CA2068215C - Analog to digital conversion with noise reduction - Google Patents
Analog to digital conversion with noise reductionInfo
- Publication number
- CA2068215C CA2068215C CA002068215A CA2068215A CA2068215C CA 2068215 C CA2068215 C CA 2068215C CA 002068215 A CA002068215 A CA 002068215A CA 2068215 A CA2068215 A CA 2068215A CA 2068215 C CA2068215 C CA 2068215C
- Authority
- CA
- Canada
- Prior art keywords
- excitation
- interval
- time
- integration
- hertz
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Lifetime
Links
Classifications
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03M—CODING; DECODING; CODE CONVERSION IN GENERAL
- H03M1/00—Analogue/digital conversion; Digital/analogue conversion
- H03M1/06—Continuously compensating for, or preventing, undesired influence of physical parameters
- H03M1/0617—Continuously compensating for, or preventing, undesired influence of physical parameters characterised by the use of methods or means not specific to a particular type of detrimental influence
- H03M1/0634—Continuously compensating for, or preventing, undesired influence of physical parameters characterised by the use of methods or means not specific to a particular type of detrimental influence by averaging out the errors, e.g. using sliding scale
- H03M1/0656—Continuously compensating for, or preventing, undesired influence of physical parameters characterised by the use of methods or means not specific to a particular type of detrimental influence by averaging out the errors, e.g. using sliding scale in the time domain, e.g. using intended jitter as a dither signal
- H03M1/0658—Continuously compensating for, or preventing, undesired influence of physical parameters characterised by the use of methods or means not specific to a particular type of detrimental influence by averaging out the errors, e.g. using sliding scale in the time domain, e.g. using intended jitter as a dither signal by calculating a running average of a number of subsequent samples
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03M—CODING; DECODING; CODE CONVERSION IN GENERAL
- H03M1/00—Analogue/digital conversion; Digital/analogue conversion
- H03M1/004—Reconfigurable analogue/digital or digital/analogue converters
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03M—CODING; DECODING; CODE CONVERSION IN GENERAL
- H03M1/00—Analogue/digital conversion; Digital/analogue conversion
- H03M1/12—Analogue/digital converters
- H03M1/50—Analogue/digital converters with intermediate conversion to time interval
- H03M1/52—Input signal integrated with linear return to datum
Abstract
An analog-to digital converter (10) employs a capacitor circuit (12) for integrating a sample of an input signal (20) during a predetermined interval of time and, thereafter, the capacitor (42) is discharged at a predetermined rate until the intergration voltage is equal to that of a reference. The discharge time serves as a measure of the amplitude of the input signal. A measurement interval is established which is equal to an integral number of cycles of each of the possible values of frequency of the A.C.
excitation. The signal integration interval has a duration less than or approximately equal to the shortest period of the A.C. exitation, this being the period of the highest frequency A.C. excitation. The signal integration is repeated periodically at each third half-cycle of the highest frequency excitation so that the total integration time experienced during positive half cycles is equal to that experienced during negative half cycles of any of the plurality of excitation frequencies. This cancels the effect of noise due to signal polarity.
excitation. The signal integration interval has a duration less than or approximately equal to the shortest period of the A.C. exitation, this being the period of the highest frequency A.C. excitation. The signal integration is repeated periodically at each third half-cycle of the highest frequency excitation so that the total integration time experienced during positive half cycles is equal to that experienced during negative half cycles of any of the plurality of excitation frequencies. This cancels the effect of noise due to signal polarity.
Description
CA 0206821~ 1998-06-03 ANALOG TO DIGITAL CONVERSION WITH NOISE REDUCTION
BACKGROUND OF THE INVENTION
This invention relates to circuits for the conversion of analog signals to digital signals, which circuits are powered with D.C. (direct current) voltages derived from power supplies energized with A.C. (alternating current) voltage such as 50 or 60 Hertz voltage and, more particularly, to the construction of such a circuit with dual slope integration over a time interval commensurate to the periods of the two A.C. voltages to reduce the affect of noise on output 2~82~ ~
signals of the converter circuit from the ~.C.
voltages.
Analog-to-digital converters are employed frequently i the measurement of signals, such as those of biological experiments, by way of example, to convert analog values of measured signals to digitally formatted signals suitable for processing by a digital computer.
Many forms of these circuits are known. It is common practice in the construction of these circuits to employ D.C. voltages to operate components of the circuits, such as transistors and integrated circuit:
from which these circuits are constructed. Ideally, the digital conver~er should be powered by a battery so as to avoid 50 or 60 Hertz hum, or similar noise whicll enters into power supplies which employ A.C. voltage as the primary source of power. I~owever, in many situations it is necessary to employ A.C. power as the primary source of power to be converted to a regulated D.C. power which is then applied to operate the analog-to-digital converter. As a result, during measurement~ of high precision, such as may be employed in biological testing, the desired precision is reduced due to noise influence from the A.C. power.
SUMMARY OF THE INVENTION
The foregoing problem is overcome and other advantages are provided by an analog-to-digital converter which, in accordance with the invention, employs dual slope integration and timing circuitry for operating each integration periodically over a measurement interval - commensurate with the periods of the A.C. excitation which powers the converter. The periodicity of the integration intervals is selected so that certain circuit integration intervals occur during positive half cycles of the A.C. excitation while other integration intervals occur during negative half cycles of the A.C. excitation. The amount of integration time occurring during a totality of positive half cycles is equal to the amount of integration time occurrinq during a totality of negative half cycles so that any influences of noise associated with positive polarity of a positive half cycle is cancelled essentially by noise associated with negative polarity of a negative half cycle.
According to an object of an aspect of the present invention is an analog-to-digital converter which comprises an integration circuit including an integrator for integrating an input signal; means for discharging the integrator at a predetermined rate to obtain a measure of an amplitude of the input signal, the integrating occurring during a first interval of time, the discharging occurring during a second interval of time immediately following the first interval of time, an elapsed time of the discharging having a duration which is longer than the first interval and serving as a measure of the amplitude of the input signal, a sum of the first and the second intervals being a composite interval; and wherein the integration circuit is operative in response to electric power obtained from A.C. excitation at any one of a plurality of frequencies commensurate in terms of a common measurement interval equal to an integral number of periods of the excitation at each of the plurality of frequencies, one of the excitation frequencies being 60 Hertz and a second of the excitation frequencies being 50 Hertz, the common measurement interval being equal to six periods of the 60 Hertz excitation, to five periods of the 50 Hertz excitation, and to four of the composite intervals to remove noise associated with the 50 Hertz and the 60 Hertz excitation; and the CA 0206821~ 1998-06-03 converter further comprises timing means for operating the integration circuit periodically to provide an even integral number of the composite intervals during the common measurement interval, the timing means including means for strobing the integration circuit to perform the integrating during the first interval of time in each of the composite intervals; and means for measuring the elapsed time of a discharging during each of the composite intervals, the measuring means outputting an average value of elapsed time measured during a succession of composite intervals occurring within the single common measurement interval, the average value of elapsed time being proportional to an amplitude of the input signal substantially free of interference from the A.C. excitation.
The invention is readily demonstrated by use of a converter which is to be powered by either 60 llertz excitation or 50 l~ertz excitation. I{erein, there is a common measurement interval of 6 periods of the A.C.
excitation at 60 Hertz, this measurement interval being equal to 5 periods of A.C. excitation at the 50 i-lertz.
Therefore, by developing a sequence of integrations of the input signal, which integrations repeat periodically over the measurement interval, it is possible to have an equal number of the integrations occur during positive and negative half cycles of the A.C. excitation.
With respect to the integration, the dual slope integration provides for paired integrations, preferably by a capacitor, wherein a first inteyration of each pair is obtained during a sampling interval of the signal being measured, and the second integration provides for a reduction in stored charge, or dischargc of the capacitor, through a predetermined resistive path. This allows the value of the integrated signal 2~21~
to be compared to a reference by a comparator.
Thereafter, there is a dead time preparatory to initiation of the next signal sample integration. The signal sample integration is of a fixed predetermine~
duration so that the voltage produced by the integrating element, a capacitor in the preferred embodiment of the invention, is a measure of signal amplitude.
The capacitor discharge of the ensuing integration, which may be referred to as the reference integration, has a varying duration depending on the amount of charge which must be discharged from the capacitor to reduce the value of integrated voltage to a value e~ual to that of the re~erence. Therefore, the length of the reference integration time is a measure of the input signal amplitude. A timing circuit, such as a counter driven by clock pulses, is employed to measure the duration of the reference integration and thereby establish a numerical value of the amplitude of the signal being measured.
As an example in the use of the invention with S0 llertz and 60 Hertz excitation, the signal integration is accomplished over a predetermined interval of time which is set approximately equal to, or less than one half of the shortest period of the A.C. excitation to allow adequate time for discharging the capacitor and resetting the integrator. The shortest period occurs with the 60 Hertz excitation. Accordingly, the signal integration time is set to a value less than or - approximately equal to 8.33 milliseconds. Furthermore, in accordance with the arrangement of the sequence of integrations, the signal integration is to be repeated - , :
206821~
at every third half-cycle of the higher frequency excitation, this being every third half-cycle of the 60 Hertz excitation. This allows for an elapsed time of a full cycle of the 60 Hertz excitation to accomplisll the S reference i~tegration and a dead time for resetting the integrator.
Upon comparing these integration intervals with the elapsed tlme in half-cycles of the lower frequency excitation, namely the 50 Hertz excitation, it is noted that in the foregoing example, the signal integration time is shorter than a half-cycle of the 50 l~ertz excitation. The invention is operative with longer signal integration times if desired, but the forcgoing temporal relationship is employed in a preferred embodiment of the invention. Vpon a superposition of the signal integration intervals upon the 50 l~ertz wave form during the measurement interval, it is observed that there is a total of four signal integrations during the measurement intPrval with the first signal integration occurring during a first half cycle of the Hertz excitation, a second signal integration interval occurring partly in a third and partly in a fourth half-cycle of the 50 Hertz excitation, a third signal intégration occurring during a sixth half-cycle of the 50 ~ertz excitation, and a fourth signal integration occurring partly in the eighth and partly in the ninth half-cycle of the 50 l~ertz excitation.
There is a total of ten half-cycles of the 50 ~lertz excitation and a total of 12 half-cycles of the G0 }~ertz excitation occurring during one measurement interval. With either excitation, the total of the signal duration times in all of the positive half cycles is equal to the total signal integration times , , .
- : : .' ;.
2~6821~
in all of the negative half cycles. Therefore, for either excitation frequency, full cancellation of noise associated with signal polarity is obtained by the invention. It i5 noted such cancellation can be provided in a single cycle but with a much longcr overall conversion cycle.
E3RIEF DESCRIPTION OF THE: DRAWINGS
The foregoing aspects and other features of the invention are explained in the following description, taken in connection with the accompanying drawing wherein Fig. 1 is a schematic diagram of the analog-to-di~ital converter of the invention including connections with system timing and a microprocessor;
Fig. 2 is a diagram of the system timing of Fig. l; and Fig. 3 is a timing diagram showing waveforms of A.C.
excitation for components of the converter and registration with a sequence of sampling intervals of the converter.
DETA I LED DES CR I PTI ON
Fig. 1 shows a schematic drawing of a converter 10 of analog voltage to digital count. In accordance with the invention, the converter 10 comprises an integrator 12, a comparator 14 connected to an output terminal of the integrator 12 at line 16, and a switch 18 which connects an input terminal of the integrator 12 at line 20 to a source 22 of input signal. An output terminal 2~6~21 ~
of the comparator 14, at line 24, connects with a system timing unit 26. The timing unit 26 is operative with a microprocessor 28 coupled thereto.
By way of example in the use of the converter 10, the input signal source 22 is shown as test equipment for biological testing. A biological sample 30, indicated in phantom, has internal resistance represented by a resistor 32 through which an electric current can be impressed by a battery 34. In the source 22, the battery 34 is connected serially with the resistor 32 by a current measuring resistor 36 having much smaller resistance than the resis~ance of the resistor 32 so as to have no more than insignificant effect on thc magnitude of current flowing through the r~sistor 32.
A voltage drop across the resistor 36 between terminal 38 and ground serves as a measure of: the current flowing through the biological sample 30, and also serves as the input signal to the converter 10.
In accordance with a feature of the invention, the integrator 12 comprises an operational amplifier 40 with a capacitor 42 connected in a feedback path between an output terminal of the amplifier 40, at lin~
16, and an inverting input terminal 44 of the amplifier 40. The electric power for operation of the amplifier 40 is provided by a pair of terminals 46 and 48 which connect with terminals 50 and 52, respectively, of a D.C. power supply 54. The power supply 54, in turn, is energized with alternating current and voltage from an A.C. power source 56. ~y way of example, the power supply 54 may be a regulated power supply which converts A.C. voltage to D.C. voltage. The A.C.
voltage may operate, by way of example, at one of the - 2a~2l~
~1 frequencies commonly used for the transmission of ~.C.
power, such as 50 or 60 Hertz, and may col~tain harmonics of these fequencies. The comparator 14, which may also be constructed in the form of an operational amplifier, includes terminals 58 and 60 connected respectively to the terminals 50 and 52 of the power supply 54 to receive electric power for operation of the comparator 14.
The switch 18 is a three-position selector switch electronically actuated by a signal on line 62 from the timing unit 26. In the center position, as shown, a movable contact 64 connects the input signal sourcc 22 to the input terminal of the integrator 12 at line 20.
The input signal at line 20 is applied via an input resistor 66 to the inverting input terminal 44 of the amplifier 40. There are two other positions for the switch contact 64, namely, the terminal of a calibration reference voltage source 68 and a ground terminal 70. The switch 18 has been portrayed as a mechanical switch for simplicity of description;
however, it is to be understood that in a preferred embodiment of the invention, the switch 18 is to be fabricated as an electronic switch.
In operation, the converter 10 receives an input signal sample upon a switching of the switch contact 64 from the ground terminal 70 to the input signal at terminal 38. At the conclusion of a signal sampling interval, the contact 64 returns to the ground terminal 70.
During the sampling interval, the signal sample is ~: applied via the resistor 66 to the amplifier 40 with the result that the signal sample is integrated by the capacitor ~2 to provide an integra~ed form of the 2~6~2~
g signal sample at line 1~. At the conclusion of the input signal sample, upon return of the switch contact 64 to ~he ground terminal 70, the ground voltage is treated by the integrator 12 as a further input signal - 5 which is integrated. This results in a reduction o~the charge stored in the capacitor 42, a discharge of the capacitor 42 which occurs at a substantially linear rate. Thus, in response to a succession of signal samples provided by the switch 18, the output voltage of the integrator 12 on line 16 rises and falls periodically for the case of a constant voltage at the input signal. This is depicted in the third trace of the graph of Fig. 3. The time required to dischar~e the capacitor 42 to reduce the output integrator voltage to a value equal to the reference voltaye of the comparator 14 is directly proportional to the amplitude of the input signal of the source 22. It is noted that all sampling intervals are of equal length to ensure the proportional relationship of stored charge in the capacitor 42 to input signal amplitude.
In view of the fact that the foregoing discharge time of the capacitor 42 is directly proportional to input signal amplitude, an accurate measurement of input signal amplitude is made by measuring the time required to discharge the capacitor 42 a sufficient amount to bring the integrator outpu~ voltage to a level equal to that of the comparator reference signal. By way of example, the inverting input terminal of the comparator 14 is connected to ground to serve as a reference input voltage; however, the inverting input terminal could be connected to some other magnitude of reference voltage if desired. Similarly, the connection of the non-inverting input terminal of the amplifier 40 to . .
:, ' , ~ . . .
20~821~
- ' 10 ground could, if desired, be altered to provide for connection to some other magnitude of voltage reference.
S In accordance with the invention, a counter 72 in the timing unit 26 counts clock pulses for the duration of the foregoing discharge time of the capacitor 42. In view of the fact that the discharge of the capacitor 42 occurs at a substantially linear rate in the manner of a negative integration, the foregoing discharge interval is identified in Fig. 3 as the reference integration, while the integration of the signal sample is identified as the signal integration in Fig. 3. An output count of the counter 72 on line 7~ i5 proportional to the input signal at terminal 38 and, therefore, serves as a measure of the input signal at terminal 38. Clock pulses from a clock 76 (Fig. 2) are applied via a logic unit 78 to the counter 72. The logic unit 78 is responsive to a timinq signal of the microprocessor 28 for initiating a counting by the counter 72, and is responsive furthermore to an output - signal of the comparator 14 provided upon the attainment of an equality between the output voltage of the integrator 12 and the comparator reference voltage.
In response to a strobing of the logic unit 78 by the comparator 14, the logic unit 78 terminates the flow of clock pulses to the counter 72 so that the count of the counter 72 is a correct measure of the reference integration time and of the input signal voltage of the source 22.
'~r "
With reference to Fig. 2, the system timinq unit 26 further comprises two latches 80 and 82, three counters 84, 86 and 88, and an output bus driver 90. In 1' 2~g821 ~
oper~tion, the microprocessor 28 down loads into the latch 80 the duration of the signal sampling interval which, by way of example, is shown as 8 milliseconds (ms). in the third trace of Fig. 3. In the example depicted in Fig. 3, the remaining tilne until initiation of the next sampling is 17 ms to give a total duration of 25 ms to the composite sampling interval. The composite sampling interval is equal to the sum of the sampling time, the maximum amount of time allowed for the reference integration, and time for resetting the integrator 12 by allowing the input terminal of the integrator 12 to remain at zero volts. In the example of Fig. 3, the maximum allowable time for th¢ sum of the reference integration and zero integration (resct) intervals is 17 ms. If desired, the signal intc~r~tion time can be increased to 8.33 ms, this being the len~th of l/2-cycle of 60 Hertz excitation, in which case the maximum allowable time for the reference integration and zero inteqration would be 16.67 ms The maximu~
allowable time for the reference integration is loaded by the microprocessor 28 into the latch 82.
The counter 86 counts the duration of time elapsing during each of the foregoing intervals, namely the signal integration time, the maximum allowable reference integration time along with the reset interval time. To accomplish the timing of the signal integration, the integration time is down loaded from the latch 80 into the counter 86 which then counts down to zero, whereupon the counter 86 outputs a pulse signal to designate the end of the signal integration interval. The counter 86 operates by counting clock pulses applied by the clock 76 via the logic unit 78, .. . .
the clock pulses being divided by 16 at counter ~4, to the counter 86.
The maximum allowable duration of the reference integration interval is established by down loadinq the length of the interval from the latch 82 to the counter 86. The counter 86 then counts down to zero whereupon comparator 14 changes state, and reset is initiated for the remainder of the interval.
Upon inspection of Fig. 3, it is noted that there is a succession of four integration cycles depicted i~ the third trace. This provides for establishing a sequence of four measurements of the output voltage of the source 22, and an averaging of the four measurements.
In order to accomplish the sequence of four measurements, the counter 88 is employed to count the successive occurrences of the sequence of four measurement intervals and the corresponding four integration cycles. The four cycles are presented by way of example. If desired, integration can be accomplished over a sequence of eight measurement cycles, in which case the counter 8~ is employed to count the eight cycles.
The logic unit 78 is responsive to counts of the counter 88 to cycle through the sequence of four integration cycles. The logic unit first down loads the signal integrate time to the counter 86. At the conclusion of the signal integration interval, the counter 86 signals the logic unit 7~ to down load the reference integration time into the counter 86. At the conclusion of the maximum allowable reference integration time, and when the comparator 14 changes 13 2~6821~
state, the reset interval is imposed. Thereupon, the count of the counter 88 is incremented to indicate completion of one of the integration cycles depicted in the third trace of Fig. 3. Also, at the beginning of the signal integration interval, the logic unit 78 places the switch contact 64 to the output terminal 38 of the source 22 and, subsequently, at the inception of the reference integration interval, places the switch contact 64 at the ground terminal 70 as has been described hereinabove. Also, as has been noted hereinabove, the logic unit 78 activates the counter 72 at the beginning of the reference integration intcrval to measure the discharge time.
Output values of the digital signals provided by the counter 86, the logic unit 78, and the counter 72, are coupled via tri-state bus buffers of the driver 90 to the microprocessor 28 for the logging in of data. A
convenience in the averaging of the signal amplitudes obtained during the seqùence of four measurement intervals is obtained by use of the counter 72 in the following manner. Upon the completion of the counting of the capacitor discharge time during the first of the four integration cycles, the count in the counter 72 is retained. Thereupon, during the next integration cycle, the next measurement count is added to the previously stored count. This procedure continues throughout the sequence of the four integration cycles to provide a total count at the conclusion of the four in*egration cycles. This count is proportional to the average value of four measurements of the input signal voltage obtained during the sequence of four measurements. In response to a signal outputted by the counter 88, which signal designates the completion of 206821~
the sequence of four measurements, the logic unit 78 directs the outputting of the count from the counter 72 to the microprocessor 28, this being following by a resetting of the counter 72 to zero. Alternately, counter 72 may be preloaded from the microprocessor 28 where the preload represents a system offset correction.
The theory of operation of the invention is explained with reference to the ~hree traces of ~ig. 3. The upper trace shows the waveform of a 50 ~lertz alternating current reduced by the A.C. source 56 (Fig.
l). The second trace shows the waveform of a 60 llcrtz - alternating current which may be produced, ; 15 alternatively, by the A.C. source 56. Thc t~o waveforms are commensurate over a common interval of lO0 ms, indicated on the time axis at the top of Fig.
BACKGROUND OF THE INVENTION
This invention relates to circuits for the conversion of analog signals to digital signals, which circuits are powered with D.C. (direct current) voltages derived from power supplies energized with A.C. (alternating current) voltage such as 50 or 60 Hertz voltage and, more particularly, to the construction of such a circuit with dual slope integration over a time interval commensurate to the periods of the two A.C. voltages to reduce the affect of noise on output 2~82~ ~
signals of the converter circuit from the ~.C.
voltages.
Analog-to-digital converters are employed frequently i the measurement of signals, such as those of biological experiments, by way of example, to convert analog values of measured signals to digitally formatted signals suitable for processing by a digital computer.
Many forms of these circuits are known. It is common practice in the construction of these circuits to employ D.C. voltages to operate components of the circuits, such as transistors and integrated circuit:
from which these circuits are constructed. Ideally, the digital conver~er should be powered by a battery so as to avoid 50 or 60 Hertz hum, or similar noise whicll enters into power supplies which employ A.C. voltage as the primary source of power. I~owever, in many situations it is necessary to employ A.C. power as the primary source of power to be converted to a regulated D.C. power which is then applied to operate the analog-to-digital converter. As a result, during measurement~ of high precision, such as may be employed in biological testing, the desired precision is reduced due to noise influence from the A.C. power.
SUMMARY OF THE INVENTION
The foregoing problem is overcome and other advantages are provided by an analog-to-digital converter which, in accordance with the invention, employs dual slope integration and timing circuitry for operating each integration periodically over a measurement interval - commensurate with the periods of the A.C. excitation which powers the converter. The periodicity of the integration intervals is selected so that certain circuit integration intervals occur during positive half cycles of the A.C. excitation while other integration intervals occur during negative half cycles of the A.C. excitation. The amount of integration time occurring during a totality of positive half cycles is equal to the amount of integration time occurrinq during a totality of negative half cycles so that any influences of noise associated with positive polarity of a positive half cycle is cancelled essentially by noise associated with negative polarity of a negative half cycle.
According to an object of an aspect of the present invention is an analog-to-digital converter which comprises an integration circuit including an integrator for integrating an input signal; means for discharging the integrator at a predetermined rate to obtain a measure of an amplitude of the input signal, the integrating occurring during a first interval of time, the discharging occurring during a second interval of time immediately following the first interval of time, an elapsed time of the discharging having a duration which is longer than the first interval and serving as a measure of the amplitude of the input signal, a sum of the first and the second intervals being a composite interval; and wherein the integration circuit is operative in response to electric power obtained from A.C. excitation at any one of a plurality of frequencies commensurate in terms of a common measurement interval equal to an integral number of periods of the excitation at each of the plurality of frequencies, one of the excitation frequencies being 60 Hertz and a second of the excitation frequencies being 50 Hertz, the common measurement interval being equal to six periods of the 60 Hertz excitation, to five periods of the 50 Hertz excitation, and to four of the composite intervals to remove noise associated with the 50 Hertz and the 60 Hertz excitation; and the CA 0206821~ 1998-06-03 converter further comprises timing means for operating the integration circuit periodically to provide an even integral number of the composite intervals during the common measurement interval, the timing means including means for strobing the integration circuit to perform the integrating during the first interval of time in each of the composite intervals; and means for measuring the elapsed time of a discharging during each of the composite intervals, the measuring means outputting an average value of elapsed time measured during a succession of composite intervals occurring within the single common measurement interval, the average value of elapsed time being proportional to an amplitude of the input signal substantially free of interference from the A.C. excitation.
The invention is readily demonstrated by use of a converter which is to be powered by either 60 llertz excitation or 50 l~ertz excitation. I{erein, there is a common measurement interval of 6 periods of the A.C.
excitation at 60 Hertz, this measurement interval being equal to 5 periods of A.C. excitation at the 50 i-lertz.
Therefore, by developing a sequence of integrations of the input signal, which integrations repeat periodically over the measurement interval, it is possible to have an equal number of the integrations occur during positive and negative half cycles of the A.C. excitation.
With respect to the integration, the dual slope integration provides for paired integrations, preferably by a capacitor, wherein a first inteyration of each pair is obtained during a sampling interval of the signal being measured, and the second integration provides for a reduction in stored charge, or dischargc of the capacitor, through a predetermined resistive path. This allows the value of the integrated signal 2~21~
to be compared to a reference by a comparator.
Thereafter, there is a dead time preparatory to initiation of the next signal sample integration. The signal sample integration is of a fixed predetermine~
duration so that the voltage produced by the integrating element, a capacitor in the preferred embodiment of the invention, is a measure of signal amplitude.
The capacitor discharge of the ensuing integration, which may be referred to as the reference integration, has a varying duration depending on the amount of charge which must be discharged from the capacitor to reduce the value of integrated voltage to a value e~ual to that of the re~erence. Therefore, the length of the reference integration time is a measure of the input signal amplitude. A timing circuit, such as a counter driven by clock pulses, is employed to measure the duration of the reference integration and thereby establish a numerical value of the amplitude of the signal being measured.
As an example in the use of the invention with S0 llertz and 60 Hertz excitation, the signal integration is accomplished over a predetermined interval of time which is set approximately equal to, or less than one half of the shortest period of the A.C. excitation to allow adequate time for discharging the capacitor and resetting the integrator. The shortest period occurs with the 60 Hertz excitation. Accordingly, the signal integration time is set to a value less than or - approximately equal to 8.33 milliseconds. Furthermore, in accordance with the arrangement of the sequence of integrations, the signal integration is to be repeated - , :
206821~
at every third half-cycle of the higher frequency excitation, this being every third half-cycle of the 60 Hertz excitation. This allows for an elapsed time of a full cycle of the 60 Hertz excitation to accomplisll the S reference i~tegration and a dead time for resetting the integrator.
Upon comparing these integration intervals with the elapsed tlme in half-cycles of the lower frequency excitation, namely the 50 Hertz excitation, it is noted that in the foregoing example, the signal integration time is shorter than a half-cycle of the 50 l~ertz excitation. The invention is operative with longer signal integration times if desired, but the forcgoing temporal relationship is employed in a preferred embodiment of the invention. Vpon a superposition of the signal integration intervals upon the 50 l~ertz wave form during the measurement interval, it is observed that there is a total of four signal integrations during the measurement intPrval with the first signal integration occurring during a first half cycle of the Hertz excitation, a second signal integration interval occurring partly in a third and partly in a fourth half-cycle of the 50 Hertz excitation, a third signal intégration occurring during a sixth half-cycle of the 50 ~ertz excitation, and a fourth signal integration occurring partly in the eighth and partly in the ninth half-cycle of the 50 l~ertz excitation.
There is a total of ten half-cycles of the 50 ~lertz excitation and a total of 12 half-cycles of the G0 }~ertz excitation occurring during one measurement interval. With either excitation, the total of the signal duration times in all of the positive half cycles is equal to the total signal integration times , , .
- : : .' ;.
2~6821~
in all of the negative half cycles. Therefore, for either excitation frequency, full cancellation of noise associated with signal polarity is obtained by the invention. It i5 noted such cancellation can be provided in a single cycle but with a much longcr overall conversion cycle.
E3RIEF DESCRIPTION OF THE: DRAWINGS
The foregoing aspects and other features of the invention are explained in the following description, taken in connection with the accompanying drawing wherein Fig. 1 is a schematic diagram of the analog-to-di~ital converter of the invention including connections with system timing and a microprocessor;
Fig. 2 is a diagram of the system timing of Fig. l; and Fig. 3 is a timing diagram showing waveforms of A.C.
excitation for components of the converter and registration with a sequence of sampling intervals of the converter.
DETA I LED DES CR I PTI ON
Fig. 1 shows a schematic drawing of a converter 10 of analog voltage to digital count. In accordance with the invention, the converter 10 comprises an integrator 12, a comparator 14 connected to an output terminal of the integrator 12 at line 16, and a switch 18 which connects an input terminal of the integrator 12 at line 20 to a source 22 of input signal. An output terminal 2~6~21 ~
of the comparator 14, at line 24, connects with a system timing unit 26. The timing unit 26 is operative with a microprocessor 28 coupled thereto.
By way of example in the use of the converter 10, the input signal source 22 is shown as test equipment for biological testing. A biological sample 30, indicated in phantom, has internal resistance represented by a resistor 32 through which an electric current can be impressed by a battery 34. In the source 22, the battery 34 is connected serially with the resistor 32 by a current measuring resistor 36 having much smaller resistance than the resis~ance of the resistor 32 so as to have no more than insignificant effect on thc magnitude of current flowing through the r~sistor 32.
A voltage drop across the resistor 36 between terminal 38 and ground serves as a measure of: the current flowing through the biological sample 30, and also serves as the input signal to the converter 10.
In accordance with a feature of the invention, the integrator 12 comprises an operational amplifier 40 with a capacitor 42 connected in a feedback path between an output terminal of the amplifier 40, at lin~
16, and an inverting input terminal 44 of the amplifier 40. The electric power for operation of the amplifier 40 is provided by a pair of terminals 46 and 48 which connect with terminals 50 and 52, respectively, of a D.C. power supply 54. The power supply 54, in turn, is energized with alternating current and voltage from an A.C. power source 56. ~y way of example, the power supply 54 may be a regulated power supply which converts A.C. voltage to D.C. voltage. The A.C.
voltage may operate, by way of example, at one of the - 2a~2l~
~1 frequencies commonly used for the transmission of ~.C.
power, such as 50 or 60 Hertz, and may col~tain harmonics of these fequencies. The comparator 14, which may also be constructed in the form of an operational amplifier, includes terminals 58 and 60 connected respectively to the terminals 50 and 52 of the power supply 54 to receive electric power for operation of the comparator 14.
The switch 18 is a three-position selector switch electronically actuated by a signal on line 62 from the timing unit 26. In the center position, as shown, a movable contact 64 connects the input signal sourcc 22 to the input terminal of the integrator 12 at line 20.
The input signal at line 20 is applied via an input resistor 66 to the inverting input terminal 44 of the amplifier 40. There are two other positions for the switch contact 64, namely, the terminal of a calibration reference voltage source 68 and a ground terminal 70. The switch 18 has been portrayed as a mechanical switch for simplicity of description;
however, it is to be understood that in a preferred embodiment of the invention, the switch 18 is to be fabricated as an electronic switch.
In operation, the converter 10 receives an input signal sample upon a switching of the switch contact 64 from the ground terminal 70 to the input signal at terminal 38. At the conclusion of a signal sampling interval, the contact 64 returns to the ground terminal 70.
During the sampling interval, the signal sample is ~: applied via the resistor 66 to the amplifier 40 with the result that the signal sample is integrated by the capacitor ~2 to provide an integra~ed form of the 2~6~2~
g signal sample at line 1~. At the conclusion of the input signal sample, upon return of the switch contact 64 to ~he ground terminal 70, the ground voltage is treated by the integrator 12 as a further input signal - 5 which is integrated. This results in a reduction o~the charge stored in the capacitor 42, a discharge of the capacitor 42 which occurs at a substantially linear rate. Thus, in response to a succession of signal samples provided by the switch 18, the output voltage of the integrator 12 on line 16 rises and falls periodically for the case of a constant voltage at the input signal. This is depicted in the third trace of the graph of Fig. 3. The time required to dischar~e the capacitor 42 to reduce the output integrator voltage to a value equal to the reference voltaye of the comparator 14 is directly proportional to the amplitude of the input signal of the source 22. It is noted that all sampling intervals are of equal length to ensure the proportional relationship of stored charge in the capacitor 42 to input signal amplitude.
In view of the fact that the foregoing discharge time of the capacitor 42 is directly proportional to input signal amplitude, an accurate measurement of input signal amplitude is made by measuring the time required to discharge the capacitor 42 a sufficient amount to bring the integrator outpu~ voltage to a level equal to that of the comparator reference signal. By way of example, the inverting input terminal of the comparator 14 is connected to ground to serve as a reference input voltage; however, the inverting input terminal could be connected to some other magnitude of reference voltage if desired. Similarly, the connection of the non-inverting input terminal of the amplifier 40 to . .
:, ' , ~ . . .
20~821~
- ' 10 ground could, if desired, be altered to provide for connection to some other magnitude of voltage reference.
S In accordance with the invention, a counter 72 in the timing unit 26 counts clock pulses for the duration of the foregoing discharge time of the capacitor 42. In view of the fact that the discharge of the capacitor 42 occurs at a substantially linear rate in the manner of a negative integration, the foregoing discharge interval is identified in Fig. 3 as the reference integration, while the integration of the signal sample is identified as the signal integration in Fig. 3. An output count of the counter 72 on line 7~ i5 proportional to the input signal at terminal 38 and, therefore, serves as a measure of the input signal at terminal 38. Clock pulses from a clock 76 (Fig. 2) are applied via a logic unit 78 to the counter 72. The logic unit 78 is responsive to a timinq signal of the microprocessor 28 for initiating a counting by the counter 72, and is responsive furthermore to an output - signal of the comparator 14 provided upon the attainment of an equality between the output voltage of the integrator 12 and the comparator reference voltage.
In response to a strobing of the logic unit 78 by the comparator 14, the logic unit 78 terminates the flow of clock pulses to the counter 72 so that the count of the counter 72 is a correct measure of the reference integration time and of the input signal voltage of the source 22.
'~r "
With reference to Fig. 2, the system timinq unit 26 further comprises two latches 80 and 82, three counters 84, 86 and 88, and an output bus driver 90. In 1' 2~g821 ~
oper~tion, the microprocessor 28 down loads into the latch 80 the duration of the signal sampling interval which, by way of example, is shown as 8 milliseconds (ms). in the third trace of Fig. 3. In the example depicted in Fig. 3, the remaining tilne until initiation of the next sampling is 17 ms to give a total duration of 25 ms to the composite sampling interval. The composite sampling interval is equal to the sum of the sampling time, the maximum amount of time allowed for the reference integration, and time for resetting the integrator 12 by allowing the input terminal of the integrator 12 to remain at zero volts. In the example of Fig. 3, the maximum allowable time for th¢ sum of the reference integration and zero integration (resct) intervals is 17 ms. If desired, the signal intc~r~tion time can be increased to 8.33 ms, this being the len~th of l/2-cycle of 60 Hertz excitation, in which case the maximum allowable time for the reference integration and zero inteqration would be 16.67 ms The maximu~
allowable time for the reference integration is loaded by the microprocessor 28 into the latch 82.
The counter 86 counts the duration of time elapsing during each of the foregoing intervals, namely the signal integration time, the maximum allowable reference integration time along with the reset interval time. To accomplish the timing of the signal integration, the integration time is down loaded from the latch 80 into the counter 86 which then counts down to zero, whereupon the counter 86 outputs a pulse signal to designate the end of the signal integration interval. The counter 86 operates by counting clock pulses applied by the clock 76 via the logic unit 78, .. . .
the clock pulses being divided by 16 at counter ~4, to the counter 86.
The maximum allowable duration of the reference integration interval is established by down loadinq the length of the interval from the latch 82 to the counter 86. The counter 86 then counts down to zero whereupon comparator 14 changes state, and reset is initiated for the remainder of the interval.
Upon inspection of Fig. 3, it is noted that there is a succession of four integration cycles depicted i~ the third trace. This provides for establishing a sequence of four measurements of the output voltage of the source 22, and an averaging of the four measurements.
In order to accomplish the sequence of four measurements, the counter 88 is employed to count the successive occurrences of the sequence of four measurement intervals and the corresponding four integration cycles. The four cycles are presented by way of example. If desired, integration can be accomplished over a sequence of eight measurement cycles, in which case the counter 8~ is employed to count the eight cycles.
The logic unit 78 is responsive to counts of the counter 88 to cycle through the sequence of four integration cycles. The logic unit first down loads the signal integrate time to the counter 86. At the conclusion of the signal integration interval, the counter 86 signals the logic unit 7~ to down load the reference integration time into the counter 86. At the conclusion of the maximum allowable reference integration time, and when the comparator 14 changes 13 2~6821~
state, the reset interval is imposed. Thereupon, the count of the counter 88 is incremented to indicate completion of one of the integration cycles depicted in the third trace of Fig. 3. Also, at the beginning of the signal integration interval, the logic unit 78 places the switch contact 64 to the output terminal 38 of the source 22 and, subsequently, at the inception of the reference integration interval, places the switch contact 64 at the ground terminal 70 as has been described hereinabove. Also, as has been noted hereinabove, the logic unit 78 activates the counter 72 at the beginning of the reference integration intcrval to measure the discharge time.
Output values of the digital signals provided by the counter 86, the logic unit 78, and the counter 72, are coupled via tri-state bus buffers of the driver 90 to the microprocessor 28 for the logging in of data. A
convenience in the averaging of the signal amplitudes obtained during the seqùence of four measurement intervals is obtained by use of the counter 72 in the following manner. Upon the completion of the counting of the capacitor discharge time during the first of the four integration cycles, the count in the counter 72 is retained. Thereupon, during the next integration cycle, the next measurement count is added to the previously stored count. This procedure continues throughout the sequence of the four integration cycles to provide a total count at the conclusion of the four in*egration cycles. This count is proportional to the average value of four measurements of the input signal voltage obtained during the sequence of four measurements. In response to a signal outputted by the counter 88, which signal designates the completion of 206821~
the sequence of four measurements, the logic unit 78 directs the outputting of the count from the counter 72 to the microprocessor 28, this being following by a resetting of the counter 72 to zero. Alternately, counter 72 may be preloaded from the microprocessor 28 where the preload represents a system offset correction.
The theory of operation of the invention is explained with reference to the ~hree traces of ~ig. 3. The upper trace shows the waveform of a 50 ~lertz alternating current reduced by the A.C. source 56 (Fig.
l). The second trace shows the waveform of a 60 llcrtz - alternating current which may be produced, ; 15 alternatively, by the A.C. source 56. Thc t~o waveforms are commensurate over a common interval of lO0 ms, indicated on the time axis at the top of Fig.
3. During this common interval of time, there is produced an integral number of cycles of the 50 }~ertz waveform and an inteqral number of cycles of the 60 Hertz waveform. There are five ~ull cycles of the 50 Hertz waveform and six full cycles of the 60 I~ertz waveform during this common measurement interval.
Therefore, any sequence of measurements which is 2~ accomplished during this common measurement interval of lOo ms can be repeated during a subsequent interval of - lO0 ms. This common -~sl~rement interval is the basic interval during which measurements are made by the converter 10 of the invention, this interval being equal to the length of time of the four integration cycles depicted in the third trace of Fig. 3.
It is a purpose of the invention to cancel the effect of any remaining A.C. ripple on the D.C. voltage J
2~6321~
provided by the supply 54 ~Fig. 1). The effect of the ripple voltage may be notecl in ~he measurement of the input signa7 voltage because ths output voltage of the supply 54 is applied to terminals of ths amplifier 40 and the comparator 14. It is presumed that any deviation from the correct measurement will have a sense depending on the polarity of the ripple voltage Thus, by way of example, if a positive polarity of ripple, present during a measurement interval, were to produce an erroneous increase in the measurement, then a negative voltage of the ripple, present during a subsequent measurement interval, would produce an erroneous decrease in the measurement. By averaging over an even number o f the positive and the negative deviations, these deviations cancel.
Upon inspection of Fig. 3, it is noted that shaded regions in the two upper traces correspond to the signal integration intervals of the third trace. The shaded region are drawn in temporal registration with the signal integration intervals. With respect to the A.C. waveform of the first trace, it may be observed by inspection that an averaging of the four shaded regions produces a net value of zero. Similarly, with respect to the A.C. waveform of the second trace, an averaging of the four shaded regions, two of which are positive and two of which are negative, produces a net value of zero. Therefore, it is concluded that deviations in the measurement of ~he input signal voltage are essentially compensated or cancelled by the foregoing timing of the measurements and the averaging of the measurements. This cancellation applies also to harmonics of 50 and 60 Hertz.
2~6821~
]6 With respect to the selection of the co~mon measurement interval equal to five cycles of the 50 l~ertz waveform and six cycles of the 60 I{ertz waveform, it is noted that the shaded regions of the 50 ~lertz waveform begin at zero-crossings of every third half-cycle of the waveform. In the case of the 50 Hertz waveform, the first shaded region begins at the zero crossing~ the second shaded region begins at one quarter cycle beyond the zero crossing, the third shaded region begins at the zero crossing but extending in the negative direction, and the fourth shaded region begins one quarter cycle after a zero crossing, also in the negative direction. This relationship arises because of the fact that the signal integration intervals arc synchronized to begin at zero crossings of t~le Go Hertz, or highest frequency, waveform, and because of the use of the common measurement interval of the integral number of cycles of the two A.C. waveforms.
It is noted also that the signal integration interval may be equal to, less than, or somewhat larger than one half cycle of the higher frequency waveform and still produce the foregoing cancellation effect. of course, if the signal integration interval is excessively long, little time remains for measuring the length of the capacitor discharge time. Also, it is noted that the integration cycles of the third trace need not be synchronized with the 60 Hertz wave form, but must have the same periodicity to allow for the proper averaging.
The foregoing construction has proven to be advantageous in providing a smaller, less expensive, integrating capactor. Also, the total conversion cycle is accomplished in 0.1 seconds.
~821~
Let it be understood that the the foregoing description is only illustrative of the invention. Various alternatives and modifications can be devised by those skilled in the art without departing from the spirit of the invention. Accordingly, the present invention is intended to embrace all such alternatives, modifications and variances which fall within the scope of the appended claims.
Therefore, any sequence of measurements which is 2~ accomplished during this common measurement interval of lOo ms can be repeated during a subsequent interval of - lO0 ms. This common -~sl~rement interval is the basic interval during which measurements are made by the converter 10 of the invention, this interval being equal to the length of time of the four integration cycles depicted in the third trace of Fig. 3.
It is a purpose of the invention to cancel the effect of any remaining A.C. ripple on the D.C. voltage J
2~6321~
provided by the supply 54 ~Fig. 1). The effect of the ripple voltage may be notecl in ~he measurement of the input signa7 voltage because ths output voltage of the supply 54 is applied to terminals of ths amplifier 40 and the comparator 14. It is presumed that any deviation from the correct measurement will have a sense depending on the polarity of the ripple voltage Thus, by way of example, if a positive polarity of ripple, present during a measurement interval, were to produce an erroneous increase in the measurement, then a negative voltage of the ripple, present during a subsequent measurement interval, would produce an erroneous decrease in the measurement. By averaging over an even number o f the positive and the negative deviations, these deviations cancel.
Upon inspection of Fig. 3, it is noted that shaded regions in the two upper traces correspond to the signal integration intervals of the third trace. The shaded region are drawn in temporal registration with the signal integration intervals. With respect to the A.C. waveform of the first trace, it may be observed by inspection that an averaging of the four shaded regions produces a net value of zero. Similarly, with respect to the A.C. waveform of the second trace, an averaging of the four shaded regions, two of which are positive and two of which are negative, produces a net value of zero. Therefore, it is concluded that deviations in the measurement of ~he input signal voltage are essentially compensated or cancelled by the foregoing timing of the measurements and the averaging of the measurements. This cancellation applies also to harmonics of 50 and 60 Hertz.
2~6821~
]6 With respect to the selection of the co~mon measurement interval equal to five cycles of the 50 l~ertz waveform and six cycles of the 60 I{ertz waveform, it is noted that the shaded regions of the 50 ~lertz waveform begin at zero-crossings of every third half-cycle of the waveform. In the case of the 50 Hertz waveform, the first shaded region begins at the zero crossing~ the second shaded region begins at one quarter cycle beyond the zero crossing, the third shaded region begins at the zero crossing but extending in the negative direction, and the fourth shaded region begins one quarter cycle after a zero crossing, also in the negative direction. This relationship arises because of the fact that the signal integration intervals arc synchronized to begin at zero crossings of t~le Go Hertz, or highest frequency, waveform, and because of the use of the common measurement interval of the integral number of cycles of the two A.C. waveforms.
It is noted also that the signal integration interval may be equal to, less than, or somewhat larger than one half cycle of the higher frequency waveform and still produce the foregoing cancellation effect. of course, if the signal integration interval is excessively long, little time remains for measuring the length of the capacitor discharge time. Also, it is noted that the integration cycles of the third trace need not be synchronized with the 60 Hertz wave form, but must have the same periodicity to allow for the proper averaging.
The foregoing construction has proven to be advantageous in providing a smaller, less expensive, integrating capactor. Also, the total conversion cycle is accomplished in 0.1 seconds.
~821~
Let it be understood that the the foregoing description is only illustrative of the invention. Various alternatives and modifications can be devised by those skilled in the art without departing from the spirit of the invention. Accordingly, the present invention is intended to embrace all such alternatives, modifications and variances which fall within the scope of the appended claims.
Claims (2)
1. An analog-to-digital converter comprising:
an integration circuit including an integrator for integrating an input signal;
means for discharging the integrator at a predetermined rate to obtain a measure of an amplitude of the input signal, said integrating occurring during a first interval of time, said discharging occurring during a second interval of time immediately following said first interval of time, an elapsed time of said discharging having a duration which is longer than said first interval and serving as a measure of the amplitude of said input signal, a sum of said first and said second intervals being a composite interval; and wherein said integration circuit is operative in response to electric power obtained from A.C.
excitation at any one of a plurality of frequencies commensurate in terms of a common measurement interval equal to an integral number of periods of the excitation at each of said plurality of frequencies, one of said excitation frequencies being 60 Hertz and a second of said excitation frequencies being 50 Hertz, said common measurement interval being equal to six periods of the 60 Hertz excitation, to five periods of the 50 Hertz excitation, and to four of said composite intervals to remove noise associated with the 50 Hertz and the 60 Hertz excitation; and said converter further comprises timing means for operating said integration circuit periodically to provide an even integral number of said composite intervals during said common measurement interval, said timing means including means for strobing said integration circuit to perform said integrating during said first interval of time in each of said composite intervals; and means for measuring the elapsed time of a discharging during each of said composite intervals, said measuring means outputting an average value of elapsed time measured during a succession of composite intervals occurring within the single common measurement interval, the average value of elapsed time being proportional to an amplitude of the input signal substantially free of interference from the A.C. excitation.
an integration circuit including an integrator for integrating an input signal;
means for discharging the integrator at a predetermined rate to obtain a measure of an amplitude of the input signal, said integrating occurring during a first interval of time, said discharging occurring during a second interval of time immediately following said first interval of time, an elapsed time of said discharging having a duration which is longer than said first interval and serving as a measure of the amplitude of said input signal, a sum of said first and said second intervals being a composite interval; and wherein said integration circuit is operative in response to electric power obtained from A.C.
excitation at any one of a plurality of frequencies commensurate in terms of a common measurement interval equal to an integral number of periods of the excitation at each of said plurality of frequencies, one of said excitation frequencies being 60 Hertz and a second of said excitation frequencies being 50 Hertz, said common measurement interval being equal to six periods of the 60 Hertz excitation, to five periods of the 50 Hertz excitation, and to four of said composite intervals to remove noise associated with the 50 Hertz and the 60 Hertz excitation; and said converter further comprises timing means for operating said integration circuit periodically to provide an even integral number of said composite intervals during said common measurement interval, said timing means including means for strobing said integration circuit to perform said integrating during said first interval of time in each of said composite intervals; and means for measuring the elapsed time of a discharging during each of said composite intervals, said measuring means outputting an average value of elapsed time measured during a succession of composite intervals occurring within the single common measurement interval, the average value of elapsed time being proportional to an amplitude of the input signal substantially free of interference from the A.C. excitation.
2. A converter according to Claim 1 wherein said first interval of time is equal in duration to one-half cycle of the 60 Hertz excitation.
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| US451,212 | 1989-12-15 | ||
| US07/451,212 US4999632A (en) | 1989-12-15 | 1989-12-15 | Analog to digital conversion with noise reduction |
| PCT/US1990/007503 WO1991009470A1 (en) | 1989-12-15 | 1990-12-14 | Analog to digital conversion with noise reduction |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CA2068215A1 CA2068215A1 (en) | 1991-06-16 |
| CA2068215C true CA2068215C (en) | 1999-06-01 |
Family
ID=23791259
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CA002068215A Expired - Lifetime CA2068215C (en) | 1989-12-15 | 1990-12-14 | Analog to digital conversion with noise reduction |
Country Status (8)
| Country | Link |
|---|---|
| US (1) | US4999632A (en) |
| EP (1) | EP0505496B1 (en) |
| JP (1) | JP2793910B2 (en) |
| AT (1) | ATE158680T1 (en) |
| CA (1) | CA2068215C (en) |
| DE (1) | DE69031498T2 (en) |
| ES (1) | ES2107453T3 (en) |
| WO (1) | WO1991009470A1 (en) |
Families Citing this family (67)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP3046327B2 (en) * | 1990-06-28 | 2000-05-29 | 安藤電気株式会社 | Control method of double integral type A / D converter |
| US5274375A (en) * | 1992-04-17 | 1993-12-28 | Crystal Semiconductor Corporation | Delta-sigma modulator for an analog-to-digital converter with low thermal noise performance |
| KR0139835B1 (en) * | 1992-07-29 | 1998-07-15 | 사또오 후미오 | D/a converter and a/d converter |
| US5385846A (en) * | 1993-06-03 | 1995-01-31 | Boehringer Mannheim Corporation | Biosensor and method for hematocrit determination |
| US5719572A (en) * | 1994-07-08 | 1998-02-17 | Cirrus Logic, Inc. | Digital signal processor with reduced pattern dependent noise |
| US5801652A (en) * | 1994-07-08 | 1998-09-01 | Cirrus Logic, Inc. | Pattern dependent noise reduction in a digital processing circuit utilizing image circuitry |
| AU3373297A (en) * | 1996-06-17 | 1998-01-07 | Mercury Diagnostics Inc. | Electrochemical test device and related methods |
| US6001239A (en) | 1998-09-30 | 1999-12-14 | Mercury Diagnostics, Inc. | Membrane based electrochemical test device and related methods |
| CA2547299C (en) | 1997-12-04 | 2009-03-03 | Roche Diagnostics Corporation | Instrument and method |
| US5997817A (en) | 1997-12-05 | 1999-12-07 | Roche Diagnostics Corporation | Electrochemical biosensor test strip |
| ES2326145T3 (en) | 1997-12-22 | 2009-10-01 | Roche Diagnostics Operations, Inc. | Measuring device. |
| US8071384B2 (en) | 1997-12-22 | 2011-12-06 | Roche Diagnostics Operations, Inc. | Control and calibration solutions and methods for their use |
| US7390667B2 (en) * | 1997-12-22 | 2008-06-24 | Roche Diagnostics Operations, Inc. | System and method for analyte measurement using AC phase angle measurements |
| US7407811B2 (en) * | 1997-12-22 | 2008-08-05 | Roche Diagnostics Operations, Inc. | System and method for analyte measurement using AC excitation |
| US6294062B1 (en) | 1998-06-01 | 2001-09-25 | Roche Diagnostics Corporation | Method and device for electrochemical immunoassay of multiple analytes |
| US7045054B1 (en) * | 1999-09-20 | 2006-05-16 | Roche Diagnostics Corporation | Small volume biosensor for continuous analyte monitoring |
| US6767440B1 (en) * | 2001-04-24 | 2004-07-27 | Roche Diagnostics Corporation | Biosensor |
| US6645359B1 (en) | 2000-10-06 | 2003-11-11 | Roche Diagnostics Corporation | Biosensor |
| US6413395B1 (en) | 1999-12-16 | 2002-07-02 | Roche Diagnostics Corporation | Biosensor apparatus |
| US6428664B1 (en) | 2000-06-19 | 2002-08-06 | Roche Diagnostics Corporation | Biosensor |
| US6488828B1 (en) | 2000-07-20 | 2002-12-03 | Roche Diagnostics Corporation | Recloseable biosensor |
| US6814843B1 (en) | 2000-11-01 | 2004-11-09 | Roche Diagnostics Corporation | Biosensor |
| US6540890B1 (en) | 2000-11-01 | 2003-04-01 | Roche Diagnostics Corporation | Biosensor |
| US6447657B1 (en) | 2000-12-04 | 2002-09-10 | Roche Diagnostics Corporation | Biosensor |
| US7473398B2 (en) | 2001-05-25 | 2009-01-06 | Roche Diagnostics Operations, Inc. | Biosensor |
| US6814844B2 (en) * | 2001-08-29 | 2004-11-09 | Roche Diagnostics Corporation | Biosensor with code pattern |
| US6755949B1 (en) | 2001-10-09 | 2004-06-29 | Roche Diagnostics Corporation | Biosensor |
| US7018843B2 (en) * | 2001-11-07 | 2006-03-28 | Roche Diagnostics Operations, Inc. | Instrument |
| US7285198B2 (en) * | 2004-02-23 | 2007-10-23 | Mysticmd, Inc. | Strip electrode with conductive nano tube printing |
| NO317076B1 (en) * | 2002-04-29 | 2004-08-02 | Idex Asa | Method and system for painting properties of a surface |
| US7572237B2 (en) | 2002-11-06 | 2009-08-11 | Abbott Diabetes Care Inc. | Automatic biological analyte testing meter with integrated lancing device and methods of use |
| US7718439B2 (en) | 2003-06-20 | 2010-05-18 | Roche Diagnostics Operations, Inc. | System and method for coding information on a biosensor test strip |
| US8148164B2 (en) * | 2003-06-20 | 2012-04-03 | Roche Diagnostics Operations, Inc. | System and method for determining the concentration of an analyte in a sample fluid |
| US8206565B2 (en) | 2003-06-20 | 2012-06-26 | Roche Diagnostics Operation, Inc. | System and method for coding information on a biosensor test strip |
| US8058077B2 (en) | 2003-06-20 | 2011-11-15 | Roche Diagnostics Operations, Inc. | Method for coding information on a biosensor test strip |
| US7488601B2 (en) | 2003-06-20 | 2009-02-10 | Roche Diagnostic Operations, Inc. | System and method for determining an abused sensor during analyte measurement |
| US7645373B2 (en) * | 2003-06-20 | 2010-01-12 | Roche Diagnostic Operations, Inc. | System and method for coding information on a biosensor test strip |
| US7645421B2 (en) * | 2003-06-20 | 2010-01-12 | Roche Diagnostics Operations, Inc. | System and method for coding information on a biosensor test strip |
| US7597793B2 (en) * | 2003-06-20 | 2009-10-06 | Roche Operations Ltd. | System and method for analyte measurement employing maximum dosing time delay |
| US7452457B2 (en) * | 2003-06-20 | 2008-11-18 | Roche Diagnostics Operations, Inc. | System and method for analyte measurement using dose sufficiency electrodes |
| ES2392170T3 (en) | 2003-07-01 | 2012-12-05 | F. Hoffmann-La Roche Ag | Electrochemical affinity biosensor system and methods of use |
| EP1713926B1 (en) | 2004-02-06 | 2012-08-01 | Bayer HealthCare, LLC | Oxidizable species as an internal reference for biosensors and method of use |
| DE102004023145A1 (en) * | 2004-05-07 | 2005-11-24 | Endress + Hauser Wetzer Gmbh + Co. Kg | Device for analog / digital conversion of a measuring voltage |
| DE102004036352B4 (en) * | 2004-05-27 | 2007-10-25 | Atmel Germany Gmbh | Circuit for current measurement and current monitoring and their use for a functional unit |
| US7556723B2 (en) * | 2004-06-18 | 2009-07-07 | Roche Diagnostics Operations, Inc. | Electrode design for biosensor |
| US7569126B2 (en) | 2004-06-18 | 2009-08-04 | Roche Diagnostics Operations, Inc. | System and method for quality assurance of a biosensor test strip |
| GB0509919D0 (en) * | 2005-05-16 | 2005-06-22 | Ralph Ellerker 1795 Ltd | Improvements to door closure system |
| KR101321296B1 (en) | 2005-07-20 | 2013-10-28 | 바이엘 헬스케어 엘엘씨 | Gated amperometry temperature determination |
| JP5671205B2 (en) | 2005-09-30 | 2015-02-18 | バイエル・ヘルスケア・エルエルシー | Gated voltammetry |
| EP1776925A1 (en) * | 2005-10-20 | 2007-04-25 | Roche Diagnostics GmbH | Analyzing means with lancet and test element |
| WO2009076302A1 (en) | 2007-12-10 | 2009-06-18 | Bayer Healthcare Llc | Control markers for auto-detection of control solution and methods of use |
| US7746257B2 (en) * | 2008-05-07 | 2010-06-29 | Cirrus Logic, Inc. | Delta-sigma analog-to-digital converter circuit having reduced sampled reference noise |
| US8009077B1 (en) | 2009-06-08 | 2011-08-30 | Cirrus Logic, Inc. | Delta-sigma analog-to-digital converter (ADC) circuit with selectively switched reference |
| US9086439B2 (en) * | 2011-02-25 | 2015-07-21 | Maxim Integrated Products, Inc. | Circuits, devices and methods having pipelined capacitance sensing |
| CN103392162B (en) | 2011-02-25 | 2016-08-24 | 高通技术公司 | Capacitive touch sense architecture |
| US8860432B2 (en) | 2011-02-25 | 2014-10-14 | Maxim Integrated Products, Inc. | Background noise measurement and frequency selection in touch panel sensor systems |
| EP2909606B1 (en) | 2012-10-17 | 2023-12-06 | University Of Maryland | Device and methods of using device for detection of aminoacidopathies |
| PL2972268T3 (en) | 2013-03-15 | 2017-10-31 | Hoffmann La Roche | Methods of failsafing electrochemical measurements of an analyte as well as devices, apparatuses and systems incorporating the same |
| JP6352954B2 (en) | 2013-03-15 | 2018-07-04 | エフ．ホフマン−ラ ロシュ アーゲーＦ． Ｈｏｆｆｍａｎｎ−Ｌａ Ｒｏｃｈｅ Ａｋｔｉｅｎｇｅｓｅｌｌｓｃｈａｆｔ | Method and device for using information from recovery pulses in electrochemical analyte measurement, apparatus and system incorporating them |
| EP2972260B1 (en) | 2013-03-15 | 2018-07-11 | Roche Diabetes Care GmbH | Methods of scaling data used to construct biosensor algorithms |
| WO2014140177A2 (en) | 2013-03-15 | 2014-09-18 | Roche Diagnostics Gmbh | Methods of detecting high antioxidant levels during electrochemical measurements and failsafing an analyte concentration therefrom as well as devices, apparatuses and systems incorporting the same |
| DK3039422T3 (en) | 2013-08-30 | 2019-03-25 | Univ Maryland | DEVICE AND METHODS FOR USING THE DEVICE FOR THE DETECTION OF HYPERAMMONIA |
| US20170198329A1 (en) | 2014-04-17 | 2017-07-13 | University Of Maryland, College Park | Device and methods of using device for detection of aminoacidopathies |
| KR102007585B1 (en) | 2014-11-03 | 2019-08-05 | 에프. 호프만-라 로슈 아게 | Electrode arrangements for electrochemical test elements and methods of use thereof |
| US10591495B2 (en) | 2015-04-27 | 2020-03-17 | University Of Maryland, College Park | Device and methods of using device for detection of hyperammonemia |
| JP2019529935A (en) | 2016-10-05 | 2019-10-17 | エフ ホフマン−ラ ロッシュ アクチェン ゲゼルシャフト | Detection reagents and electrode arrangements for multi-sample diagnostic test elements and methods of using them |
| CN111537875B (en) * | 2020-06-01 | 2021-03-05 | 泉州睿郎机电技术有限公司 | Method and device for collecting and measuring switching time of double-power-supply change-over switch contact |
Family Cites Families (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE2059862C3 (en) * | 1969-12-08 | 1973-12-13 | Iwasaki Tsushinki K.K., Tokio | Analog to digital converter and use of an integrator |
| GB1361613A (en) * | 1970-11-24 | 1974-07-30 | Solartron Electronic Group | Analogue to digital converters |
| US3696403A (en) * | 1970-11-25 | 1972-10-03 | Gordon Eng Co | Low level conversion system |
| US4633221A (en) * | 1983-10-24 | 1986-12-30 | Intersil, Inc. | Dual slope analog-to-digital converter with automatic, short cycle range determination |
| US4656459A (en) * | 1985-10-07 | 1987-04-07 | Intersil, Inc. | Dual slope converter with large apparent integrator swing |
| US4908623A (en) * | 1988-08-08 | 1990-03-13 | Honeywell Inc. | Apparatus and method for range control and supply voltage compensation in a dual slope analog to digital converter |
-
1989
- 1989-12-15 US US07/451,212 patent/US4999632A/en not_active Expired - Lifetime
-
1990
- 1990-12-14 AT AT91902620T patent/ATE158680T1/en active
- 1990-12-14 DE DE69031498T patent/DE69031498T2/en not_active Expired - Lifetime
- 1990-12-14 EP EP91902620A patent/EP0505496B1/en not_active Expired - Lifetime
- 1990-12-14 CA CA002068215A patent/CA2068215C/en not_active Expired - Lifetime
- 1990-12-14 WO PCT/US1990/007503 patent/WO1991009470A1/en active IP Right Grant
- 1990-12-14 ES ES91902620T patent/ES2107453T3/en not_active Expired - Lifetime
- 1990-12-14 JP JP3502860A patent/JP2793910B2/en not_active Expired - Lifetime
Also Published As
| Publication number | Publication date |
|---|---|
| EP0505496A4 (en) | 1994-10-26 |
| DE69031498T2 (en) | 1998-02-05 |
| JP2793910B2 (en) | 1998-09-03 |
| JPH05502772A (en) | 1993-05-13 |
| DE69031498D1 (en) | 1997-10-30 |
| ATE158680T1 (en) | 1997-10-15 |
| US4999632A (en) | 1991-03-12 |
| WO1991009470A1 (en) | 1991-06-27 |
| EP0505496A1 (en) | 1992-09-30 |
| ES2107453T3 (en) | 1997-12-01 |
| CA2068215A1 (en) | 1991-06-16 |
| EP0505496B1 (en) | 1997-09-24 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CA2068215C (en) | Analog to digital conversion with noise reduction | |
| US5998971A (en) | Apparatus and method for coulometric metering of battery state of charge | |
| US5363047A (en) | Portable ground fault detector | |
| JPS6166971A (en) | Method and circuit for measuring resistance of temperature detector and digitizing it | |
| US4238784A (en) | Electronic measuring system with pulsed power supply and stability sensing | |
| JPS58105625A (en) | Multiplexed analog-to-digital converter | |
| US4558301A (en) | Voltage-to-frequency and analog-to-digital converter circuit | |
| GB2076547A (en) | Resistance Measuring Circuit | |
| SU1621052A1 (en) | Device for integrating electric signals with background component | |
| JPS5563768A (en) | Threshold voltage measuring instrument | |
| RU1810848C (en) | Equipment for testing parameters of semiconductor devices | |
| RU174465U1 (en) | DEVICE FOR DIAGNOSTIC OF INSULATION OF ELECTRIC MACHINE WINDING | |
| JPH0245154B2 (en) | DENRYUSOKUTEISOCHI | |
| SU1350585A1 (en) | Device for non-contact measurement of liquid electric conduction | |
| SU1091090A1 (en) | Phase-meter | |
| JP2555711B2 (en) | Signal converter | |
| SU481130A1 (en) | Device for converting signals from resistive sensors into a digital code | |
| SU1559301A1 (en) | Energy meter | |
| SU999155A1 (en) | High-frequency signal amplitude measuring device | |
| SU693229A1 (en) | Device for discriminating and storing paramagnetic resonance signal | |
| JPH09275343A (en) | A/d converter for weight inspection device | |
| SU674212A1 (en) | Digital meter of monopulse signals | |
| SU958981A1 (en) | Stroboscopic compensating signal converter | |
| RU1794752C (en) | Track circuit | |
| SU900217A1 (en) | Digital resistance meter |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| EEER | Examination request | ||
| MKEX | Expiry |