CN100588123C - Receiver for use in wireless communications and method and terminal using same - Google Patents
Receiver for use in wireless communications and method and terminal using same Download PDFInfo
- Publication number
- CN100588123C CN100588123C CN200580021656A CN200580021656A CN100588123C CN 100588123 C CN100588123 C CN 100588123C CN 200580021656 A CN200580021656 A CN 200580021656A CN 200580021656 A CN200580021656 A CN 200580021656A CN 100588123 C CN100588123 C CN 100588123C
- Authority
- CN
- China
- Prior art keywords
- receiver
- amplitude imbalance
- signal
- piece
- value
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Fee Related
Links
Images
Classifications
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
- H03D3/00—Demodulation of angle-, frequency- or phase- modulated oscillations
- H03D3/007—Demodulation of angle-, frequency- or phase- modulated oscillations by converting the oscillations into two quadrature related signals
- H03D3/009—Compensating quadrature phase or amplitude imbalances
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Noise Elimination (AREA)
- Circuits Of Receivers In General (AREA)
- Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
Abstract
A wireless receiver for receiving and demodulating a frequency modulated RF signal by direct conversion includes, a circuit 107,109,113 producing in-phase and quadrature components of the received signal, and an estimator 204 periodically estimating an imbalance in amplitude between the in-phase and quadrature components and applying a relative adjustment in amplitude to compensate for the detected imbalance 205. The estimator 204 (i) divides samples <B>I</B>i of the in-phase component <B>I</B><B>(t)</B> and corresponding samples <B>Q</B>i of the quadrature component <B>Q</B><B>(t)</B> into blocks; (ii) calculates for each block a block power value <B>I</B>n corresponding to a summation of values of squares of the samples <B>I</B>i and a block power value <B>Q</B>n corresponding to a summation of values of squares of the samples <B>Q</B>i; (iii) calculates from the block power values <B>I</B>n and <B>Q</B>n a block amplitude imbalance value <EMI ID=2.1 HE=12 WI=21 LX=1019 LY=2076 TI=UI> <PC>and (iv) calculates for a set of the block amplitude imbalance values an average value.
Description
Technical field
The present invention relates to a kind of receiver that in radio communication, uses and relate to method and the terminal of using this receiver.Specifically, the present invention relates to a kind of direct conversion receiver, this directly changes receiver by decomposing and use the homophase (I) and quadrature (Q) component of modulation signal, can carry out demodulation to RF (radio frequency) signal of frequency modulation(FM) (FM).
Background technology
Use direct converting structure to make up and have following problem with the I component of detection received signal and the conventional FM wireless receiver of Q component.As described below, this receiver may produce error in relative phase between I component and the Q component and amplitude.Be commonly called ' orthogonal unbalance ' this error may make the output audio signal that obtained produce distortion.Particularly suffer Rayleigh fading (being called " decline " herein) and/or have in received signal under the situation of low signal-to-noise ratio in received signal, described distortion is unacceptable for the user.Prior art can not provide a kind of scheme of gratifying solution orthogonal unbalance problem.
The present invention is specifically related to the amplitude imbalance component of orthogonal unbalance.
US5705949 has proposed a kind of be used to remove the amplitude between I component and the Q component or the method for gain error.This process need Combined Processing ability, and in fading environment, be difficult to satisfactory.
Summary of the invention
According to a first aspect of the invention, a kind of wireless receiver is provided, this wireless receiver is used to utilize direct transfer process that warbled RF signal is received and demodulation, and described wireless receiver comprises: the input signal path is used to transmit RF input received signal; Circuit is used to produce the homophase and the quadrature component of described received signal; And estimator, be used for periodically estimating the amplitude imbalance between described homophase and the quadrature component, and be used for utilization factor amplitude is revised, with to detected unbalance compensating, wherein said estimator operation is used for: (i) the sample Ii of described in-phase component I (t) and the sample Qi of the quadrature component Q (t) of correspondence are divided into piece, wherein each piece comprises a plurality of sample Ii and Qi; (ii) for each piece, calculate square value and the corresponding block power value In with described sample Ii, and the square value of calculating and described sample Qi and corresponding block power value Qn; (iii) according to described block power value In and Qn,
The computing block amplitude imbalance values
And the (iv) mean value of computing block amplitude imbalance value set.
To embodiments of the invention be described by giving an example with reference to the accompanying drawings now, wherein:
Description of drawings
Fig. 1 shows the schematic block circuit diagram of known direct conversion RF receiver.
Fig. 2 shows the schematic block circuit diagram of using direct conversion RF receiver of the present invention.
Embodiment
Fig. 1 shows known RF and directly changes FM receiver 100, and this RF directly changes the FM receiver problem that will be solved by the present invention has been described.The FM signal x (t) of input connects 103,105 input path 101 along separate routes via having, and is sent to two frequency mixers 107,109 respectively.Local oscillator 111 produces reference signal, and this reference signal has and the identical frequency of input signal x (t) carrier frequency.First component of reference signal is applied directly to frequency mixer 107, at frequency mixer 107 places, uses this first component to multiply by input signal x (t).The second component of reference signal is applied to phase shifter 113, and the phase shift of phase shifter 113 output is applied to frequency mixer 109,, uses phase shift output to multiply by input signal x (t) at these frequency mixer 109 places.Although and frequency mixer 107 and 109 combined phase shifters 113 are expected to introduce between each component of reference signal that is applied to frequency mixer 107 and 109 and have the 90 degree phase shifts of gain for " 1 ", but, in fact phase shift of being introduced and 90 degree have deviation slightly, and gain can occur different slightly with " 1 ".The output signal of self-mixing device 107 transmits by low pass filter (LPF) 115 in the future, thereby produce output in-phase component signal I (t), and the output signal of self-mixing device 109 transmits by low pass filter (LPF) 117 in the future, thereby produce output orthogonal component signal Q (t).The amplitude imbalance that is incorporated in the output of frequency mixer 109 is shown as unbalance gain A in square frame 119.
The mathematical analysis of structure shown in Figure 1 is as follows:
Input signal can be expressed as:
x(t)＝cos(wt+φ(t)+γ) x(t)＝cos(wt+φ(t)+γ)
Wherein ω is the RF carrier frequency of input rf signal x (t), and γ is that the arbitrary phase of oscillator and φ (t) are the frequency modulation(FM)s with detected x (t).
In addition, x (t)=I (t)+j*Q (t), wherein I (t) and Q (t) they are in-phase component and the quadrature component of x (t).
Wherein A represents amplitude imbalance, and α represents the phase imbalance angle between the phase angle of I (t) and Q (t).
According to embodiments of the invention, will in the following manner the component I (t) and the Q (t) that will describe be handled, that is, will describe it is estimated and applies adjusting to eliminate amplitude imbalance A.For example, as what in applicant's common unsettled UK Patent Application numbering 0411888.1, describe, also phase imbalance is estimated and eliminated phase imbalance.Component after the adjusting that obtains is made up, thus structure modulation signal φ (t), thus audio signal output is provided.
Fig. 2 shows and uses schematic block diagram of the present invention, as to be used in the circuit 200 in the direct conversion FM receiver.Each component that has same reference numbers with each component among Fig. 1 has and this component identical functions, and can be not described again.
Utilize 201 couples of output signal I (t) of connection to sample, and utilize 203 couples of output signal Q (t) of connection to sample by low pass filter (LPF) 117 by low pass filter (LPF) 115.By connecting each input that 201 and 203 each sampled signals that obtain are provided as processor 204, described processor 204 is carried out the amplitude imbalance algorithm, and this will describe after a while.The output signal of from processor 204 is amplitude imbalance correction signals, and it has pointed out the value of 1/A.This correction signal is applied to amplitude modifier 205 via connecting 202, and to eliminate detected amplitude imbalance A, wherein said amplitude modifier 205 utilization factor 1/A revise the amplitude of Q (t).
For example according to the mode described in the common unsettled UK Patent Application numbering 0411888.1 of applicant, use the phase adjusted treatment circuit (not shown) of I (t) and Q (t) sample that the phase imbalance between I (t) and the Q (t) is estimated, and having produced the phase shift control signal, this phase shift control signal is corresponding with the equal value or the inverse value of the phase imbalance of this estimation.In this way the phase adjustment signal of Gu Jiing is applied by phase shifter 207.Be applied to phase shifter 207 via being connected 226 from low pass filter 117 with the corresponding signal of quadrature component Q (t).Phase shifter 207 is carried out the phase angle adjusting thus, and described phase angle is regulated detected phase imbalance angle [alpha] is compensated.The output that is worth corresponding phase shifter 207 with the phase adjusted of Q (t) is applied to processor 209.Via connecting 224, also be used as the input of processor 209 with the corresponding signal of in-phase component I (t).Processor 209 calculates the value of merchant Q (t)/I (t) according to its each input, and will represent that this result's signal offers processor 211.Processor 211 calculates arc tangent (arctg) value by the represented merchant's parameter of the input signal of processor 209.The output signal of from processor 211 is applied to further processor 213, and the input signal of these processor 213 computation processors 213 is with respect to the differential of time t.At last, the output signal of from processor 213 is applied to audio frequency output 215.Audio frequency output 215 converters (not specifically illustrating) that comprise such as audio tweeter, this converter is converted to for example audio signal of voice messaging with the electronic signal output of from processor 213.
As follows by the amplitude imbalance algorithm that processor 204 is carried out.Obtain the sample of component I (t) and Q (t) according to the frequency of 20k samples/sec.Therefore, the duration of each sampling is the 1/20k=50 microsecond.On 500 milliseconds sampling period, carry out sampling.Therefore the sum of sample is 500 milliseconds/50 microsecond=10000 sample.Sample is divided into piece.According to the size of operating condition selection piece, this operating condition is the intensity or the S/N (signal to noise ratio) of received signal for example.For example, for the received signal intensity that is equal to or greater than threshold value or receive S/N, size that can piece is set to first value, and for received signal intensity or S/N less than threshold value, and size that can piece is set to the second bigger value.For example, for the S/N that is equal to or greater than threshold value 15dB, can there be 15 samples in each piece.Therefore in the sampling period, there be 10000/15=666 piece.For S/N, can there be 100 samples/block less than threshold value 15dB.Therefore there be 10000/100=100 piece.In fading environment, use less piece, can make this algorithm show better.
For the piece of each sample, calculate
The power value and
The power value.
For each piece, use following formula, calculate amplitude imbalance values according to the power of the sum of powers Q of I:
Thus, A
nThe piece value be the square root of the power of Q divided by the power of I.
The amplitude imbalance values of trying to achieve for each piece in the given set of blocks (for example 1000 pieces) by according to from minimum to the highest rank order.
Abandon in the ordering back set subclass of 45% the highest amplitude imbalance values, and abandon in the set of ordering back the subclass of 45% lowest block amplitude imbalance values, and only keep the subclass of the piece imbalance values of 10% between the subclass that is abandoned.Therefore 1000 pieces are for example arranged in set, then the result of 450 the highest amplitude imbalance values and 450 lowest block amplitude imbalance values is dropped, and further handles and keep 100 piece amplitude imbalance values.
According to a remaining K imbalance results, wherein K is the piece number in the residuary subset, and 10% in the set of blocks of assessing in above-mentioned example for example utilizes following formula to draw geometrical mean:
A wherein
CorrIt is the amplitude imbalance that to be corrected.Thus, A
CorrEqual the k rank root of the product that k the sampled result of A multiply each other each other.
Processor 204 outputs are corresponding to 1/A
CorrSignal, apply for amplitude modifier 205.During the cycle of received signal, the FM modulation signal that is received is carried out described algorithm continuously and adaptively.
When transmitting with relevant sub-audio signal, can operate processor 204 by any reception voice signal of receiver 200 receptions.Yet, if desired, also can only when receiver 200 receives specific input signal, optionally carry out described algorithm.For example, receiver can be operated the known analog FM signal that receives from the RF transmitter.For example, according to industrial standard TIA 603, this can be a standard FM modulation signal.
For handling the signal receive in fading environment, it is useful that a plurality of samples of processor 204 being handled according to this mode are divided into piece.If do not adopt piecemeal, then can not abandon incorrect result owing to decline.In fading environment, in signal envelope, exist fast to change.In the time of among signal is in the deep fading, the result of merchant Q/I (piece for handling when this situation of being suitable for) is (I approaches zero) or very little (Q approaches zero) very greatly.Piecemeal, sort and abandon high or low result, make to allow in amplitude imbalance estimation, can not include the incorrect result who causes by decline.In fact, wireless terminal is always operating in the fading environment probably.
The size of piece also is very important: for quick decline, less block size is optimum, and for low S/N, bigger block size is optimum.Receiver 200 can utilize known RSSI (indication of received signal intensity) constantly to measure the power of received signal.The result can be offered estimator 204, this estimator 204 can utilize the result who is provided to operate, thus the size of regulating block automatically.Suppose certain relation of existence between received signal power and reception S/N and make that S/N also is big for high received power.Use received power threshold to judge: when described received power value is equal to or greater than threshold value, to use little block size, perhaps when described received power value bigger block size of use during less than threshold value.
Only use selected amplitude imbalance result's subclass (for example only using 10% result in this example) also to have such advantage, promptly can reduce the complexity of the performed algorithm of processor 204 significantly, and reduce required signal processing amount thus.As a result, this has reduced to incorporate into the battery power consumption of the terminal that receiver 200 is arranged.
Thereby deviate can be incorporated into and provide incorrect amplitude imbalance estimation among the result owing to draw arithmetic average, therefore think that drawing geometric average is better than drawing arithmetic average.The example that this conclusion is described is as follows:
Suppose for piece 1Q1=3 and I1=2, and be 1 for block 2Q1=2 and I1=3 and A.A1=3/2 and A2=2/3.Use arithmetic average will obtain (3/2+2/3)=1.0833 to A, this is incorrect result.Yet A is used geometric average: will obtain sqrt ((3/2) * (2/3))=1, this is correct result's (wherein ' sqrt ' is square root).
Fig. 2 shows various processors.As known to those skilled in the art, these processors can be shown each discrete processors, and perhaps the function of two or more processors can be incorporated in the processor, for example, is programmed the digital signal processor with software for calculation.
The result
The algorithm of on the simulation FM tracer signal of emulation and reality processor 204 being carried out is tested.With reference to figure 2, utilize the direct conversion receiver of operating in this mode that actual signal is carried out record.According to % measuring amplitude unbalance (Amp IM)
Amp IM[%]=100e wherein e provide by following formula:
Q(t)＝Asin(φ(t)+γ+a)＝(1+e)sin(φ(t)+γ+a)
When using described algorithm, the target capabilities of error is that worst error is Amp IM=0.5%.
For the signal of the 60dbm of various true records in the fading environment at 450MHz place, measured Amp IM error and result and dropped on, and had 0.2% mean error from 0.08% in maximum 0.45% scope.Similarly, being 15dB to the signal to noise ratio scope carries out Amp IM estimation error to the various simulate signals of 35dB, and error range is that 0.08% (35dB SNR) is to 0.2% (15dB SNR).
Different is that we also use known formula
Amplitude imbalance error is estimated.In the fading signal environment, we use known procedures, have obtained Amp IM and be 4% mean error value.
When use is of the present invention in radio receiver, after having made the wireless device memory, can programme, thereby the storing initial imbalance values is with respect to the table of RF frequency to it.In wireless device operating period, imbalance values (amplitude and phase place) will change in time.Thus, can be in the unbalance information after collect upgrading between the operating period of this embodiment, and use this information so that suitable compensation to be provided, thus keep the appropriate audio output signal of quality.Can also be with the unbalance information stores upgraded in the memory of wireless device, in order to replace the information of initial storage.
General introduction
In a word, provide improving one's methods of self adaptation amplitude imbalance compensation in a kind of direct conversion receiver, and the receiver that uses this method operation is provided.
Suffer in received signal under the situation of noise and/or decline, described method has been made substantial improvement to the estimation of required imbalance compensation.
Can in the memory relevant, programme with respect to the look-up table of RF frequency to initial amplitude imbalance values with receiver, for example, in the memory of the mobile radio station that uses receiver.This can be that for example so-called code inserts (codeplug), and it has stored the operation sequence and the data of mobile radio station.
During using receiver, will gradually change in time as the amplitude imbalance of frequency function.The information that processor 204 is collected can be used for the stored information of memory is upgraded.
The present invention has improved the audio performance in the wireless terminal with receiver, and wherein said receiver is to operate on the FM analog signal under the direct translative mode.
Claims (9)
1. wireless receiver, this wireless receiver is used to utilize direct transfer process that warbled RF signal is received and demodulation, and described wireless receiver comprises: the input signal path is used to transmit RF input received signal; Circuit is used to produce the homophase and the quadrature component of described received signal; And estimator, be used for periodically estimating the amplitude imbalance A between described homophase and the quadrature component, and be used for utilization factor 1/A amplitude is revised that with to detected unbalance compensating, wherein said estimator operation is used for:
(i) with the sample I of described in-phase component I (t)
iSample Q with the quadrature component Q (t) of correspondence
iBe divided into piece, wherein each piece comprises a plurality of sample I
iAnd Q
i
(ii), calculate and described sample I for each piece
iSquare value and corresponding block power value I
n, and calculating and described sample Q
iSquare value and corresponding block power value Q
n
(iii) according to described block power value In and Qn, computing block amplitude imbalance values
And
The (iv) mean value of computing block amplitude imbalance value set.
2. according to the receiver of claim 1, wherein the described amplitude imbalance value set that has calculated mean value by described estimator is the subclass of selecting from bigger piece amplitude imbalance value set.
3. according to the receiver of claim 2, wherein said estimator operation is used for, and abandons at least one subclass of the piece amplitude imbalance value set except that selected subclass in the described bigger piece amplitude imbalance value set.
4. according to the receiver of claim 3, wherein said estimator operation is used for, size according to the piece amplitude imbalance values sorts to it, and abandon first subclass of (i) size greater than the piece amplitude imbalance values of first threshold, and (ii) abandoning second subclass of size less than the piece amplitude imbalance values of second threshold value, each in wherein said first and second threshold values is all corresponding to the subclass of the piece amplitude imbalance values with predetermined number.
5. according to the receiver of claim 4, wherein said estimator further operation is used for, from the set after the ordering, select the three subsetss of piece amplitude imbalance values, described three subsetss have the piece amplitude imbalance values that satisfies following condition, that is, described amplitude imbalance values is less than the piece amplitude imbalance values of described first subclass and greater than the piece amplitude imbalance values of described second subclass.
6. according to the receiver of claim 1, wherein said estimator operation is used for, and calculates the geometric average of described amplitude imbalance values.
7. according to the receiver of claim 1, wherein said receiver operation is used for, and only just optionally operates when receiving specific received signal, and is unbalance to estimate the current amplitude between described homophase and the quadrature component.
8. according to the receiver of claim 1, wherein said estimator operation is used for, and selects the size of sample block according in the operating condition of received signal at least one.
9. receiver according to Claim 8, wherein said estimator operation is used for, select the size of sample block according to following condition, described condition is: whether the signal to noise ratio of described received signal or received signal intensity are detected as is given threshold value at least, the selected sample block size sample block size when being described given threshold value at least when described signal to noise ratio or signal strength signal intensity whether when described signal to noise ratio or signal strength signal intensity are lower than described given threshold value.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| GB0414459.8 | 2004-06-29 | ||
| GB0414459A GB2415846B (en) | 2004-06-29 | 2004-06-29 | Receiver for use in wireless communications and method and terminal using it |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN1981437A CN1981437A (en) | 2007-06-13 |
| CN100588123C true CN100588123C (en) | 2010-02-03 |
Family
ID=32800330
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN200580021656A Expired - Fee Related CN100588123C (en) | 2004-06-29 | 2005-06-23 | Receiver for use in wireless communications and method and terminal using same |
Country Status (7)
| Country | Link |
|---|---|
| JP (1) | JP2008509577A (en) |
| CN (1) | CN100588123C (en) |
| AU (1) | AU2005267308B2 (en) |
| CA (1) | CA2572236C (en) |
| DE (1) | DE112005001456T5 (en) |
| GB (1) | GB2415846B (en) |
| WO (1) | WO2006012245A1 (en) |
Families Citing this family (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| GB2437574B (en) | 2006-04-28 | 2008-06-25 | Motorola Inc | Receiver for use in wireless communications and method of operation of the receiver |
| US8503545B2 (en) * | 2006-08-31 | 2013-08-06 | Advanced Micro Devices, Inc. | I/Q imbalance compensation |
| JP4850222B2 (en) * | 2008-08-26 | 2012-01-11 | 株式会社豊田中央研究所 | Correction method of offset amount in phased array radar |
Family Cites Families (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4696017A (en) * | 1986-02-03 | 1987-09-22 | E-Systems, Inc. | Quadrature signal generator having digitally-controlled phase and amplitude correction |
| US5901346A (en) * | 1996-12-11 | 1999-05-04 | Motorola, Inc. | Method and apparatus utilizing a compensated multiple output signal source |
| US6122325A (en) * | 1998-02-04 | 2000-09-19 | Lsi Logic Corporation | Method and system for detecting and correcting in-phase/quadrature imbalance in digital communication receivers |
| US20040013204A1 (en) * | 2002-07-16 | 2004-01-22 | Nati Dinur | Method and apparatus to compensate imbalance of demodulator |
-
2004
- 2004-06-29 GB GB0414459A patent/GB2415846B/en not_active Expired - Fee Related
-
2005
- 2005-06-23 DE DE112005001456T patent/DE112005001456T5/en not_active Ceased
- 2005-06-23 CA CA2572236A patent/CA2572236C/en not_active Expired - Fee Related
- 2005-06-23 JP JP2007519294A patent/JP2008509577A/en active Pending
- 2005-06-23 CN CN200580021656A patent/CN100588123C/en not_active Expired - Fee Related
- 2005-06-23 AU AU2005267308A patent/AU2005267308B2/en not_active Ceased
- 2005-06-23 WO PCT/US2005/022335 patent/WO2006012245A1/en active Application Filing
Also Published As
| Publication number | Publication date |
|---|---|
| CN1981437A (en) | 2007-06-13 |
| GB0414459D0 (en) | 2004-07-28 |
| GB2415846A (en) | 2006-01-04 |
| CA2572236A1 (en) | 2006-02-02 |
| GB2415846B (en) | 2006-08-02 |
| CA2572236C (en) | 2010-10-19 |
| JP2008509577A (en) | 2008-03-27 |
| AU2005267308A1 (en) | 2006-02-02 |
| DE112005001456T5 (en) | 2007-05-31 |
| WO2006012245A1 (en) | 2006-02-02 |
| AU2005267308B2 (en) | 2008-04-10 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| RU2107395C1 (en) | Device which joins received signals to phase pointers and cordless phone | |
| EP1783922B1 (en) | System and method for providing an accurate estimation of received signal interference for use in wireless communication systems | |
| CN100481828C (en) | Amplitude imbalance compensation of quadrature modulator | |
| CN1171404C (en) | High dynamic range low ripple RSSI for zero-IF or low-IF receivers | |
| US9537520B2 (en) | Method and apparatus for calibrating distortion of signals | |
| CN101461133A (en) | Automatic gain control | |
| CN1898925B (en) | Fast soft value computation methods for gray-mapped qam | |
| CN101689883B (en) | Method and apparatus for removing pilot channel amplitude dependencies from RAKE receiver output | |
| AU638362B2 (en) | Digital radio receiver having amplitude limiter and logarithmic detector | |
| US5487091A (en) | Method for determining signal usability in a diversity receiver | |
| AU749189B2 (en) | AGC circuit | |
| CN1083196C (en) | Digital transmission system comprising a receiver which includes carrier recovery circuit | |
| CN100588123C (en) | Receiver for use in wireless communications and method and terminal using same | |
| EP1488553B1 (en) | Method, arrangement and communication receiver for snir estimation | |
| US6823026B2 (en) | Apparatus and method for baseband detection | |
| EP1643635A2 (en) | Demodulator for use in wireless communications and receiver, method and terminal using it | |
| US5603112A (en) | Received signal strength indicator utilizing approximation factors and the I and Q signal components | |
| CN101010871B (en) | Receiver and method for wireless communications terminal | |
| CN102217384B (en) | Power bias report method, modulation signal sending method, mobile terminal and base station | |
| EP0717509A1 (en) | Method and apparatus for combining signals | |
| JP3441311B2 (en) | Receiving machine | |
| KR100666985B1 (en) | Method and apparatus for calibrating in adaptive array antenna system | |
| CN113395229A (en) | Coherent demodulation method and device suitable for pi/4-DQPSK and readable storage medium | |
| JP3182376B2 (en) | Diversity receiver | |
| JPH10233722A (en) | Diversity receiver |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant | ||
| C56 | Change in the name or address of the patentee |
Owner name: MOTOROLA SOLUTIONS INC. Free format text: FORMER NAME: MOTOROLA INC. |
|
| CP01 | Change in the name or title of a patent holder |
Address after: Illinois State Patentee after: MOTOROLA SOLUTIONS, Inc. Address before: Illinois State Patentee before: Motorola, Inc. |
|
| CF01 | Termination of patent right due to non-payment of annual fee |
Granted publication date: 20100203 |
|
| CF01 | Termination of patent right due to non-payment of annual fee |