CN1061312A - 用于在一个码分多址蜂窝电话系统中产生信号波形的系统与方法 - Google Patents

用于在一个码分多址蜂窝电话系统中产生信号波形的系统与方法 Download PDF

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CN1061312A
CN1061312A CN91105315A CN91105315A CN1061312A CN 1061312 A CN1061312 A CN 1061312A CN 91105315 A CN91105315 A CN 91105315A CN 91105315 A CN91105315 A CN 91105315A CN 1061312 A CN1061312 A CN 1061312A
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sequence
channel
receiver
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克莱因S·吉洛霍森
欧文M·雅各布斯
罗伯托·帕多瓦尼
林赛A·韦弗·Jr
查尔斯E·惠特利·Hr
安德鲁J·维泰尔比
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Abstract

一种使用扩展频谱通信技术进行信息信号通信 的系统和方法。多个PN序列构成在用户间提供正 交,以便减小相互之间的干扰,并允许较高的容量和 较好的链路性能。在正交代码的情况下,在一个预定 的时间区间上互相点为零,结果在正交代码之间没有 干扰,所提供的代码时间帧相互校准时间,在一个典 型的实施例中,信号在网孔站(12,14)和移动单元 (16,18)之间使用直接序列扩展频谱通信信号进行 通信。

Description

本发明涉及蜂窝电话系统,特别是涉及一种新颖的改进的系统与方法,该系统与方法采用扩展频谱通信信号,用以在一个移动蜂窝电话系统或卫星移动电话系统中传送信息。
对含有大量系统用户的通信系统起到推进作用的几种技术之一便是码分多址(CDMA)调制技术的采用。在本领域的其它公知的多址方式的通信系统有,时分多址方式(TDMA),频分多址方式(FDMA)和AM调制方案,比如说幅度压扩的信号边带调制方案。然而对于多址通信系统,CDMA的扩展频谱调制技术较之其它这些调制技术有着明显的优点。在一多址通信系统中采用CDMA技术已经在1990年2月13日出版的美国专利第4901307号,题为“采用卫星或陆地中继器的扩展频谱多址通信系统”中公开,该发明已受让给本发明的受让人,并在此引为参考。
在上面刚刚提到的专利中,公开的多址技术是用在有大量移动电话系统用户的场合,每个用户拥有一个经卫星中继器或陆地基站(也称之为网孔位置站,单元位置或简称为网孔)通信的无线电收发两用机,其中的卫星中继器和陆地基站采用了码分多址(CDMA)扩展频谱通信信号。在采用CDMA通信过程中,频谱可被再次使用多次,从而使系统的用户容量增加。CDMA的采用,使之比采用其它多址技术有高得多的频谱效率。
卫星信道尤其要经历具有瑞切安(Rician)的衰落。因而,接收的信号包含有同多个具有瑞利(Rayleigh)衰落统计的反射成分取和的直流成分。典型地,这种直流与反射成分的功率比是处于6-10dB这样一个级别上,这要取决移动单元天线的特性以及移动单元所处的环境特性。
与卫星信道相对照,陆地信道经历的信号衰落典型地包含有无直流成分的瑞利衰落成分。因此,与其中瑞切安衰落呈主导衰落的卫星信道相比,陆地信道呈现为更严重的衰落环境。
在陆地信道信号中的瑞利衰减特性是由从许多不同的物理环境被反射信号引起的。其结果是,一个信号从多个方向以不同的延迟到达一移动单元接收器。在包含有蜂窝移动电话系统的、通常被用来作为移动无线电通讯的UHF频带上,可能会发生信号穿过不同路径的严重的相位差。在有深度衰落发生的场合,可导致这种信号的破坏性累加的可能性。
移动单元的物理位置是陆地信道衰落的一个极重要的原因。移动单元在位置上的一个小变动就会改变所有信号传输路径的物理延时,从而引起各条路径的不同相位。因而,移动单元通过其环境的运动,可导致一个相当迅速的衰落过程。比如说,在一个850MHZ的蜂窝无线电频带中,对于一个以每秒中1英哩行驶的车辆,这种衰落可快到每秒钟即为一个新的衰落。如此严重的衰落构成对在陆地信道的信号的极为严重的破坏,从而导致通信质量的低劣。可采用附加的发射机功率,以克服衰落的问题。然而,这种功率的增加,在过量的功率增加中会使用户与系统的相互干扰增加。
由4901307号美国专利公开的CDMA调制技术提供了胜于采用卫星陆地中继器的通信系统中采用的窄带调制技术的许多优点。对于任何通信系统,尤其是对于多路信号,陆地信道都会产生特殊问题。通过减小多路的不利的效果,即衰落,同时也利用由此而得的优点,CDMA技术的采用使陆地信道的特殊问题得以克服。
在一个CDMA蜂窝电话系统中,同一频带可在全部单元内用于通信。CDMA提供处理增益的各种波形特性也可以用来区别占有同一频带的各种信号。进一步,高速的伪噪声(PN)调制使得许多不同的传输路径被分开,其中假设在路径延迟的差异超过PN片持续时间(Chip  duration),即1/带宽。如果在一个CDMA系统中采用大约1MHZ的一个PN片速率,等于扩展带宽与系统的数据速率之比的全扩展频谱处理增益可用来防止这样的路径:该路径与所希望的路径间的路径延迟超过1微秒。一个1微秒的路径延迟差异对应着大约1000英尺的不同路径距离。典型地,市区环境产生的不同路径延迟远超过1微秒,在某些地域可高达10-20微秒。
在一个诸如由传统电话系统所采用的模拟FM调制的窄带调制系统中,调制路径的存在导致了严重的多路径衰落。然而,借助于采用宽带CDMA调制,这种不同路径可在解调处理中被鉴别抑制。这种鉴别极大地降低了多路径衰落的严重程度。由于偶然存在有用于特定系统的,具有延迟差小于PN片时间的几个路径,在采用CDMA鉴别技术的情形中,多路径衰落并不能完全消除。在这一级别上的信号所具有的路径延迟是不能在解码器中被鉴别抑制的,从而引起了一定程度的衰落。
因而,期望可提供分集形式以使系统降低衰落。分集是一种用于减轻衰落不良影响的方法。有三种主要的分集方法:时间分集,频率分集和空间分集。
通过重复使用,时间交错和错误检测及作为一种重复形式的编码,可以得到很好的时间的分集。本发明中采用的每一个分集技术,都是以时间分集的形式出现的。
由于它作为一个宽带信号而本身固有的特性,CDMA通过扩展其信号能量于一个宽频带之上而提供了一个频率分集的形式。因而,频率选择的衰落,仅影响CDMA信号带宽的一小部分。
借助于一个移动用户通过两个或多个网孔站的同时键路提供的多个信号通路,可获得空间即路径分集。路径分集还可以由通过扩展频谱的处理而利用多路环境的方法来实现,这种扩展频谱的处理使得以不同传输路径延时到达的信号可被分别地接收和处理。路径分集的实例已在同处于受理中的下列两份美国专利申请中作了说明,“在一个CDMA蜂窝电话系统中的软过界切换”(No.07/433,030,申请日,89年11月7日);“在一个CDMA蜂窝电话系统中的分集接收器”(No.07/432552,申请日:89年11月7日)。这两份申请均受让给本发明的受让人。
通过控制发射机的功率,在一个CDMA系统中的衰落的不利影响可被进一步控制在一定的范围内。一个用于网孔站和移动单元的功率控制的系统已由美国专利申请“在一个CDMA蜂窝电话系统移动系统中用来控制发射功率的方法及设备”所公开(No.07/433031,申请日89年11月7日),该申请也为本发明受让人所受让。
由4901307号美国专利申请所公开的CDMA技术计划在移动卫星通信中链路的两个方向上采用相干调制及解调(的技术)。其中披露的是,对于卫星-移动和网孔-移动链路采用等频载波信号作为一个相干相位参考。然而在陆地蜂窝式的环境中,由于其多路衰落的严重性而导致信道的相位破坏,使之不可能使用相干解调技术于移动-网孔链路。本发明提供的装置采用的是非相干调制与解调技术,以克服在移动-网孔链路中的多路径的不利效果。
由美国4901307号专利申请所公开的CDMA技术还进一步计划采用相当长的PN序列,而每个用户信道被指定一个不相同的PN序列。对于除去零以外的全部时间移动,不同PN序列间的交叉相关和某一PN序列自相关都有为零的平均值,这使得不同的用户信号在接收上可被鉴别。
然而,这种PN信号是非正交的。虽然互相关平均为零,对于诸如一个信息比特这样短的时间间隔,交叉相关会引起一个二项分布。这样,在相同的功率频谱密度,信号的彼此干扰就完全象是为宽的带宽的高斯噪声。因此,其它的用户信号,即相互干扰的噪声,最终限制了它应实现的容量。
对于一个宽带PN  CDMA系统,多路的存在可提供路径分集。如果可以得到两个或更多的具有大于1微秒差异的路径延迟的路径,两个或更多个PN接收机可被用来分别地接收这些信号。因为这些信号将典型地表现在多路衰落方面的独立性,即,它们通常不一起衰落,这两个接收器的输出可分集结合。因此,仅在两个接收机同时都经历衰落的情况下,才发生性能上的损失。因此,本发明的一方面是提供两个或更多的、以一个分集结合器结合的PN接收机。为了利用多路信号的存在,为了克服衰落,需要采用一个波形,该波形允许实行路径分集的组合操作。
因而,本发明的一个目的是提供几个PN序列的产生,这些时序是正交的,以便减少相互干扰,从而实现更大的用户容量,并助使路径分集克服衰落。
在一个移动蜂窝电话系统中采用扩展频谱通信技术,尤其是采用CDMA技术,从而使得这种通信系统具有优于其它通信系统的极大增强其可靠性和容量的前景。前面提到的CDMA技术进一步使得诸如衰落和干扰的问题便利地得以克服。这样,CDMA技术进一步促进了频率的重复使用,从而在实际上增加了系统用户的数量。
本发明是一个新颖的和改进的方法与系统,它用来建立在用户间提供正交的PN序列,以便降低相互干扰,获得更高的容量和更好的链路工作状况。采用正交PN编码,由于其在一预定的时间间隔上的互相关是零,在提供编码时间帧彼此时间定位的情况下,将导致在正交编码间无干扰发生。
在一个实施例的实例中,在一个网孔站和几个移动单元间的信号通信,采用的是直接序列扩展频谱的通信信号。在一个网孔至移动的链路中,定义有导频、同步,寻呼和语音信道。经网孔至移动链路信道通信的信息一般是被编码的,交错的,双相移键控(BPSK)正交调制的信息,其中双相移键控调制正交覆盖每一个BPSK符号,伴随着被覆盖符号的正交相移键控(QPSK)扩展。
在移动-网孔链路中,定义有入口信道和话音信道。经移动-网孔链路的信息一般是:编码信息,交错信息,伴随QPSK扩展的正交信号信息。
通过下面结合附图的详细描述,本发明的特点、目的,与优点将会变得更加显见。在附图中,相同的参考符号始终代表着相应的同一含意。
图1是一个CDMA蜂窝电话系统的实例示意图;
图2是一个使用在CDMA蜂窝电话系统中的网孔站的方框图;
图3是一个网孔站接收机的方框图;
图4是一个网孔站发射调制器的方框图;
图5是一个同步信号符号同步化的实例定时图;
图6是一个具有正交覆盖的、同步信道定时的实例定时图;
图7是一个整个网孔-移动链路定时实例定时图;
图8是移动电话交换局设备的方框图;
图9是一个在CDMA蜂窝式电话系统中用于CDMA通信的移动单元电话构形的方框图;
图10是一个移动单元接收机的方框图;
图11是一个移动单元发射调制器的方框图;
图12是用于一个带有猝发发射可变数据速率的移动-网孔链路的实例定时图;
图13是一个总的移动-网孔链路定时的实例定时图。
实施例的详述
在一个CDMA蜂窝电话系统中,每个网孔站都有多个调制器-解调器单元或扩展频谱的调制解调器。每个调制解调器包含有一个数字扩展频谱发射调制器,至少一个数字扩展频谱数据接收器和一个搜索器接收器。按照需要,每个在网站的调制解调器被指定给一个移动单元,以实现与指定移动单元的通。
一个CDMA蜂窝电话系统采用了一个软过界切换方案,当一原有网孔路调制解调器继续服务于该呼叫时,一个新的网孔站调制解调器指定给一个移动单元。当该移动单元是处在这两个网孔站间的转换区域时,呼叫作为信号强度的指令可在网孔站间往复交换。由于移动单元总是经至少一个网孔站调制解调器进行通信的,对于移动单元或在使用中,很少发生中断的情况。因此,除去用于减小衰落效应的分集手段以外,移动单元还使用多个接收器,以便于过界切换处理。
在CDMA蜂窝电话系统中,每一个网孔站发射一个“导频载波”信号。一旦网孔分成了几个区,在该网孔中,每个区都有一相关的识别信号。这种导频信号是由移动单元所用的,以便获得初始的系统同步并提供固定的时间、频率及网孔站发送信号的相位跟踪。每个网孔站还发射扩展频谱调制的信息,例如网孔站标识、系统定时、移动寻呼信号以各种其它控制信号。
由每一网孔的每一区发出的导频信号具有相同的扩展码但有一不同的码相位偏移。相位偏移的几个导频信号之间可彼此相互地被区别,从而识别始发的网孔站或区域。使用同一导频信号码使得移动单元可借助从所有导频信号码相位中的一个搜索来找到系统的定时同步。作为由各码相位相关处理而确定的最强的导频信号,是很容易识别的。被识别的最强导频信号通常对应的是由最近的网孔站所发射的导频信号。然而,不论最强的导频信号是否为最近的网孔站所发,都将被采用。
一经获得最强的导频信号,如具有该最强导频信号的移动单元的初始同步,该移动单元寻找另一个被打算作为由在本网孔中的所有用户接收的载波。这一称为同步信道的载波发射包含着为系统中移动单元所用的系统信息的广播消息(broadcast  message)。除去传送被该移动单元采用的长PN码、交叉器帧,声码器和其它无需附加搜索用于移动单元同步的系统定时信息外,系统信息还标识出网孔站和系统。还可提供另外一个称之为寻呼信道的信道,以将消息发至移动单元,指示出已经从它们收到了呼叫,并当一个移动单元始发一个呼叫时,用信道分配对其响应。
在相应于网孔站邻近区或邻近发射导频信号的码移位点,移动单元连续扫描接收的导频载波的信号码。作这种扫描是为了确定是否有来自邻近区或网孔的导频信号已经比开始确定是最强的导频信号变得更强。当处于这种待用呼叫模式时,如果一邻近区或网孔站的导频信号变得比始发网孔站区发射的导频信号更强,移动单元将接受这个更强的导频信号和相应的新区域或网孔站的同步及寻呼信道。
当呼叫开始时,即确定一个在这一呼叫过程中使用的伪噪声(PN)编码地址。这一编码地址既可以由网孔站指定,也可以由事先的安排来确定,这要以移动单元的识别为基础。呼叫始发后,移动单元不断扫描由该网孔站发出的导频信号,除去邻近区或网孔的导频信号外,通信的建立还以这种对导频信号的扫描为基础。为了确定是否有某个相邻区或网孔发出的导频信号变得比由该移动单元所在进行通信的网孔站发出的导频信号更强,这种导频信号的扫描要连续进行。当与邻近网孔或网孔区相关的导频信号变得强于目前网孔或网孔区的导频信号,表明移动单元已经进入了一个新的网孔或网孔区,应开始进行过界切换。
一个包含本发明实施例的一个电话系统由图1示出。由图1示出的系统在系统移动单元或移动电话和网孔站间的通信中使用了扩展频谱调制技术。大城市中的蜂窝系统中,可能有数百个网孔站台,为数以百万计的移动电话提供服务。扩展频谱技术的采用,尤其是CDMA的采用,与传统的FM调制蜂窝系统相比较,极大地促进了这种规模系统的用户容量的增加。
在图1中,系统控制器和交换器10也称之为移动电话交换局(MTSO),它典型地包含有接口和处理电路,用来为网孔站的系统控制。控制器10还控制着从公共交换电话网(PSTN)适当网孔站的、用于传输到合适的移动单元的常规电话呼叫。控制单元10还控制着来自移动单元,经至少一个网孔站到PSTN的常规呼叫。由于移动单元是不直接进行相互通信的,所以控制器10还可经过合适的网孔站连接移动用户间的呼叫。
控制器10可经各种方式与网孔站相连接,比如说经专用电话线,光纤链路或微波通信链路。在图1中,示出了两个实例的这种网孔站12和14,及每个都包含有蜂窝电话的移动单元16和18。在此讨论并给出的网孔站12和14被认为服务于整个网孔。然而应当明白,网孔可被按地域划分为几个区域,每个区域可作为一个不同的服务地区来对待。相应地,作为同网孔的区域间的也作过界切换,就如同在此描述的对于多网孔一样,就象对多个网孔那样,在区域间也可实现分集。
在图1中,箭头线20a-20b和22a-22b分别表示在网孔站12和移动单元16和18间可能的通信链路。相类似地,箭头线24a-24b和26a-26b分别表示在网孔站14和移动单元16和18间可能的通信链路。网孔站12和14假定采用相同的功率发射。
网孔站的服务区域或网孔,是以地理形状来定义的,以使移动单元与一网孔站最为靠近,如果该网孔被分成几个区的话,移动单元则在一个网孔区中。如果移动单元是空闲时,即无呼叫进行时,移动单元则不停地监视着从邻近的每一网孔站发出的导频信号,并监视从分成区的网孔的单一网孔站来的导频信号是否可用。如图1所示,经通信链路20a和26a,网孔站12和14分别地将导频信号发出即正向传送到移动单元16。通过对网孔站12和14所发导频信号的强度比较,移动单元16可决定它是处在那个网孔。
在由图1所示出的实例中,移动单元16可被认为靠近网孔站12。当移动单元始发一个呼叫时,一控制消息则送到这最近的网孔站,即网孔站12。网孔站12一收到该呼叫请求消息,就将呼叫数码传到系统控制器10。随后,系统控制器10通过PSTN将呼叫与预期的接收者相联。
一旦在PSTN中始发一呼叫,控制器则将此呼叫信息发送到该地域内的所有网孔站。各个网孔站在其各自服务区域内再发出寻呼消息,该区域预期为被呼叫接收移动用户所处的区域。当这所期的接收移动单元听到该呼叫消息时,它将一个控制消息发送到最近的网孔站作为对该呼叫的响应。该控制消息通知系统控制器,这一特定的网孔站在同该移动单进行通信。随后,控制器10经该网孔站将此呼叫送到该移动单元。一旦移动单元16移出开始的网孔站12的服务区域,便要通过另一个网孔站以发送这种呼叫的方式来继续这种呼叫的尝试。
关于蜂窝电话系统,联邦通信委员会(FCC)已经拨出总共25MHz来作为移动-网孔的链路,而另25MHz作为网孔-移动的链路。FCC已经将这拨出的频段在两个服务提供者间作了等分,其中之一是作为该服务区域的有线电话公司,而另一个则要由抽彩而选择。由于这种分配所作的规定,这分配给每个载波的用于链路每个方向上的12.5MHz,被进一步再分成两个子波段。对于无线载波,该子波段一个为11MHz而另一个为1.5MHz。因此,一个带宽小于1.5MHz的信号可适于这两个子波段的任何之一,但带宽小于2.5MHz的信号可以适于这子波段,但仅适于其中之一。
为了在可使用的蜂窝电话系统的频谱上CDMA技术的使用获得最大的适应性,使用在蜂窝电话系统中的信号波形应小于1.5MHz的带宽。一个好的第二选择应该是一个大约2.5MHz的带宽,这一带宽可使有线蜂窝系统载波有完好的适应性,也可使无线蜂窝载波有几乎完好的适应性。当使用较宽的带宽时,具有提供增加多路识别的优点,而缺点在于较高的设备花费及在所处的带宽内的较低的频率分配的适应性。
在如图1所示的一个扩展频谱的蜂窝电话系统中,所实现的最佳波形设计包含有一个直序列伪噪声扩展频谱载波。该PN序列的片(chip)速率,在这最佳的实施例中,选择为1.2288MHz。选择这一特殊的片速率,为的是在滤波后导致有大约1.25MHz的带宽,这是近似于拨给一蜂窝服务载波的整个带宽的十分之一。
在选择该确定的时隙率的另外一个考虑是期望该片速率可被该系统中采用的基带数据速率确切的等分整除。还希望这除数是一个2的幂指数。在这最佳实施例中,基带数据速度是每秒9600比特,导致了1.2288MHz的选择,以128倍的9600做为PN片速率。
在网孔-移动链路中,用作分离该频谱的二进制序列可以两种不同类型的时序建立得来,每一个具有不同的几种性质以提供不同的功能。有一种可被在一个网孔或区域中的所有信号采用的外部码,被用来在多路信号间识别。这种外部码也被用来识别由不同网孔或不同区域传输到移动单元的信号。还有一种内部码,用来识别由单个区域或网孔发射的用户信号。
在最佳实施例中用于网孔站发射信号的载波波形的设计使用了一个正弦载波。该正弦载波是由一对二进制PN序列正交(四相)调制的,其中二进制PN序列提供了由由一单个区或网孔发射的外部码。这两个序列是由两个具有同样序列长度的不同PN产生器产生的。一个序列双相调制这同相载波信道(信道I),而另一个载波双相调制载波的正交相位(信道Q)。产生的信号被相加,以形成复合器相位载波。
虽然逻辑值“0”和“1”被传统地用来表示二进制的序列,在调制处理中采用的信号电压是用+V伏表示逻辑“1”而-V伏表示逻辑“0”。为正交调制一个正弦信号,电压平均值为零的正弦波,用一个乘法器电路,乘以由二进制序列控制的+V或-V电压电平。产生的信号可再由通过一带通滤波器进行带宽限制。在技术上也可先对二进制序列进行低通滤波,然后再同正弦波信号相乘,因而交换了操作顺序。一个正交调制器包含有两个双相位调制器,每一个由不同的序列所驱动,并且在两个双相调制器中采用的正弦波信号彼此产生90°的相移。
在该最佳实施例中,对于被传信号载波的序列长度被选为32768片。这种长度的序列可用增加一个零位到长度为32767的时隙序列的方法来修正最大长度线性序列产生器来产生。这样得到的序列有良好的互相关性和自相关性。良好的互相关性和自相关性对于防止由不同网孔所发的导频载波间的相互干扰是必要的。
一个这类长度的序列是希望的,为的是当移动单元首次进入系统而不知系统定时的时候,减小它们的采集时间。由于不知道定时,必须搜索该序列的整个长度以确定正确的定时。序列越长,采集搜索所需时间也就越长。虽然可用短于32768的序列,但必须懂得,随着序列长度的降低,码的处理增益也低。随着增益被降低,对于多路干扰和来自邻近网孔及其它干扰源的干扰的抑制力也被降低,可能低到不能接受的水平。因而,希望在一允许的时间内使用最长的可被采集的序列。同样希望在所有的网孔中使用相同的代码多项式,以便使得在初始采集同步信息时还不知所处的网孔的移动单元能够通过搜索一代码多项式而获得完全同步。
为简化同步处理,在一系统中的所有的网孔都被彼此同步。在一典型的实施例中,网孔的同步是通过将所有的网孔同步于一共同的参考时间来实现的。比如说奈沃斯特(Navstar)全球定位系统的卫星导航系统,是将其自身同步于世界协同时间的(UTC)。
通过提供基础序列的时间移位,来自不同网孔的信号被差异化。每一个网孔都被指定一个不同于其相邻网孔的基础序列的不同的时间位移。在最佳实施例中,32768的重复周期被分成512个时间位移。这512个位移段被隔开64个片的间距。在一个蜂窝系统中的每个网孔的每个区,也被指定有该位移中的不同的一个,为它的所有的发射所用。如果在系统中有多于512的区或网孔,则这些位移可按照在日前模拟FM蜂窝系统中频率被重复使用的方式而被重复使用。在其它的设计中,不同于512的位移可被采用。还应该考虑导频信号位移的指定问题,除非绝对必要时,相邻近的网孔不采用相邻的时间位移。
由同一网孔或该网孔的一个区所进行行的信号发射,对于I与Q信道,共用同一外部PN码。该信号还被利用由采用沃尔什(walsh)函数产生的一内部正交码扩展。编地给一特定用户的信号由被与外部PN序列和被一特定的沃尔什序列,(或几个沃尔什序列的序列)相乘,该沃尔什序列是根据用户的电话呼叫的持续期由系统控制器指定的。相同的内部码被使用I和Q信号,导致一个对该内部码的有效的双相调制。
每个长度为n的一套n个正交二进制序列,对于n的任何2的幂均能构成,这在本领域是公知的,可参见S.W  Golomb  etal的“具有空间应用的数字通信”一文(Prentice-Hall,Inc.1964年,45-64页)。事实上,正交二进制序列组公知的长度多数是大于4而小于200。易于生成的这种序列的一类称之为沃尔什函数,也叫Hadamard矩阵。
一个n阶沃尔什函数可递归定义如下:
Figure 911053158_IMG2
W′是表示为W的逻辑互补,而W(1)=|0|
因此,
Figure 911053158_IMG3
Figure 911053158_IMG4
一个沃尔什序列是沃尔什函数矩阵的一列。一个n级沃尔什函数包含有n个序列,每个长为n比特。
一个n级沃尔什函数,(以及其它正交函数)具有这样的性质,即在所有的n个码的间隔上,假设各序列是彼此时间对准的,则该序列中的所有不同序列间的相关性是零。可以从注意到每一序列与任一其它序列相比有一半的序列比特彼此不相同得到这种相关性。还应当注意到,总是有一个序列包含的都是零而其它所有序列则包含一半为零而一半为1。
相邻的网孔和区域可以再使用沃尔什序列,因为使用在相邻网孔和区域的外部PN码是各不相同的。由于对于一特定移动单元的位置和两个或更多的不同网孔间的信号的不同传播时间,对于两个网孔的某一时间的沃尔什函数正交性所要求的时间对准条件是不能满足的。因而,必须依靠外部PN码以便提供从不同网孔到达移动单元的信号间的区别。然而,由一个网孔发射的信号是彼此正交的,因而彼此之间无互扰。这就消除了多数位置上的大部分干扰,从而得到较高的容量。
本系统还力图将话音信道设计为一个可变速率信道,它的数据速率从一个数据块到另一个数据块可以是变化的,其中数据块具有一个对于控制使用的数据速率所要求的最小附加位。当有无用语言要被传输时,通过消除不必要的发射,则变化数据速率的采用降低了相互的干扰。在语言编码器中采用了几种算法,以便根据语言活动的变化在每一个语音码器数据块中产生一个比特的变化数。在动态语言期间,根据说话人的活动,语言编码器可产生包含有20,40,80或160比特的20毫秒的数据块。而且还希望在一固定的时间中通过变化发射速率发射该数据块。更进步希望无请求信令比特去通知有多少比特正在被发射。
通过采用循环冗余校验码(CRCC)进一步对数据块编码,CRCC附加给该数据块一套额外奇偶校验比特,可以用来确定该数据块是否已经被正确地解码。通过采同一预定的二进制多项式来划分该数据块的方法而产生出CRCC校验码。该CRCC包括全部或部分这种划分处理的余数比特。在接收机中,CRCC被校验,这种校验是通过再生相同的余位并检查被接收的余位是否同该再生的校验位相同来实现的。
在这公开的发明中,接收解码器解码该数据块,将其数据块视为有160比特,而后再当作有80比特等等,直至全部可能的数据块长度均已偿试过为止。CRCC用来对每一试解码进行计算。如果一试解码产生出正确的CRCC,该数据块则是可接受的并被送到语音解码器作进一步的处理。如果没有试解码产生一个有效的CRCC,所接收的符号则被送到系统的信号处理器,在那里可被选择地进行其它处理操作。
在网孔发射机中,被发射的波形的功率是随着数据块的数据速率的变化而变化的。最高的数据速率使用的载波功率也最高。当数据速率低于它的最大值时,除去降低功率外,调制器还将重复每一编码数据符号所要求的次数,以实现所希望的发射速率。举例说,处在最低的发射速率时,每个被编码的数据符号被重复4次。
在移动的发射机中,其峰值功率是恒定的,但根据被发射的数据块中的比特数,发射机选控输出的是该峰值功率的 1/2 ,或 1/4 ,或 1/8 。该发射机的接通时间的位置是随着移动用户的编地的用户码而伪随机地变化的。
网孔-移动链路
在最佳实施例中,对于网孔-移动链路沃尔什函数的尺寸n被选为64(n=64),因此,64个将发送不同信号的每一个都被指定一个单独的正交序列。对于每一个语音转换的被前向错误纠正(FEC)编码符号流,被它的指定沃尔什序列所乘。每一语言信道的该沃尔什码/FEC编码符号流则又被外部PN编码波形所乘。所生成的扩展的符号流则被相加在一块儿,以形成一复合的波形。
该生成的复合波形随后被调制在一个正弦载波上,被带通滤波,转移至所期望的工作频率,被放大并经天线系统辐射。本发明的另一实施例可交换上述的某些操作顺序以形成由网孔站发射的信号。比如说,可先用外部PN码波形乘每一个语言信道并进行滤波操作,然后再相加所有的信道的信号,以经天线辐射。在本技术领域内属于公知的是该线性操作的次序可进行交换以获得各种实施上的优点和不同的设计。
最佳实施例的、用于蜂窝电话服务的波形设计采用了如4901307号美国专利公开的导频载波方法于网孔-移动链路中。全部网孔采用同样的32768长度的序列发射导频载波,但具有不同的定时位移以防止相互的干扰。
导频波形采用全零沃尔什序列,即在全部的沃尔什函数系列中的一个全部由零构成的沃尔什序列。采用全零沃尔什序列于全部网孔的载波,使得对于导频波形的搜索可忽略沃尔什函数,直到已经得到外部码PN同步之后为止。由于沃尔什帧的长度是PN序列长度的一个因数这样一个特点,该沃尔什帧被锁定到该PN码的周期。因此,假设PN码网孔编址位移是64个片(即沃尔什帧长度)的几倍,那么从外部PN码的定时周期可隐函地了解这沃尔什帧结构。
在一服务区域内的所有网孔都被提供有准确的同步。在这最佳实施例中,处在每一网孔的GPS接收机将局部波形定时同步于世界协调时间(UTC)。GPS系统使时间同步的精确度好于1微秒。当着移动单元从一个网孔到另一个网孔并有呼叫正向发出时,希望有精确的网孔同步,以使得网孔间的过界切换可容易地实现。如果邻近的网孔被同步,移动单元则无困难地与新网孔同步,从而实现一平稳的过界切换。
导频载波要以比发射一典型的语音载波的功率更高的功率来发射,以便为该信号提供更大的信噪比,和干扰裕度。这较高的功率水平的导频载波可以使以高速实现始发的采集搜索,而且使经一相当宽的带宽相位跟踪电路实现导频载波的载波相位的极精确的跟踪成为可能。从跟踪导频信号载波而获得的载波相位被用来作为由用户信息信号调制的载波的解调参考。这一技术使很多用户载波对载波相位参考采用一共同的导频信号。比如说,在一个发射总共15个同时的话音载波的系统中,该导频载波可具有四倍于语音载波的功率。
除去导频载波外,另外一个要由在网孔中的全部系统用户所接收的载波是由网孔站发出的。这一称为同步信道的载波,同样也采用相同的32768长度的PN序列来频谱扩展,但具有一不同的压缩的沃尔什序列。该同步信道发射一个含有为系统中移动单元所采用的信息的广播消息。该系统信息标识网孔站及系统并传送信息使得长PN码被用作要被同步的移动信息信号而无需附加的搜索。
另一个信道叫作寻呼信道,可被用来发射消息至移动单元,指示已有一个对它们的呼叫已经到达,并当一个移动单元始发一呼叫时,以信道的指定对其响应。
每一个话音载波对每一个电话呼叫发射一个语言的数字表达式。模拟语言波形采用标准的数字电话技术进行数字化并采用一语言编码处理压缩成速率大约为9600比特/秒的数据。则该数字信号速率为r= 1/2 ,限制长度K=9卷积编码,采用重复,并且被交错以提供检错及校正功能,这些功能使系统工作于低得多的信/噪及干扰的比率。用于卷积编码,重复及交错的技术,在本技术领域是熟知的。
生成的编码码元与指定的沃尔什序列相乘,然而再乘外部PN码。这种处理生成-PN序列,其速率为1.2288MHz即128倍的9600比特/秒的速率。该生成信号再被调制在一个RF载波上,并且随其它话音载波一起与导引和调整载波相加。这一相加取和既可发生在与PN序列相乘以前,也可在其之后,可以在该处理中的几个不同点来完成这一相加取和,比如在IF频率,或是在基带频率。
每个语音载波还被乘以一个值,该值确立了它相对于其它语音载波功率的发射功率。这一功率控制的特征使得功率被分配到那些由于所期接收处于相对劣势的位置而要求较高的功率的那些链路。移动单元采用的、报告它们所接收信号的信噪比的装置使得其功率置在一个可提供足够的使用而无浪费的水平上。在假设时间对准被保持的情况下,沃尔什序列的正交性质不会因为采用不同的功率水平于不同的语音载波而受到干扰。
图2以方框图的形式示出了一个网孔站的实施例。在该网孔站中,采用了两个接收机系统,它们各自具有用于空间分集接收的天线和模拟接收机。在每一个这种接收系统中,信号进行完全相同的处理直到这些信号经历一个分集结合处理为止。虚线内的各部件是用来进行网孔站和一个移动单元间的通信的各单元。模拟接收器的输出也被提供给用于与其它移动单元通信的其它部件。
在图2中,第一个接收器包括有天线30,模拟接收器32,搜索器接收器34和数字数据接收器36。第一个接收机系统还可包括一个可选用的数字接收器38。第二个接收器系统包括有天线40,模拟接收器42,搜索器接收器44和数字接收器46。
网孔站还包括网孔控制处理器48。控制处理器48连同搜索器接收器34和44一起被耦合到数据接收器36、38、和46。由控制处理器48提供的多种功能,其中包括数据处理功能,定时信号的产生,功率控制,过界切换控制,分集,分集结合和系统控制处理器与MTSO(图8)的接口。沃尔什函数的指定以及发射机与接收器的指定也由控制处理器48提供。
两个接收器系统均经数据接收器36,38和46耦合到分集结合器和解码器50。数据链路52被耦合接收分集结合器和解码器电路50的输出。数据链路52还被耦合到控制处理器48,网孔站发射调制器54和MTSO数据交换器。在控制处理器48的控制下,利用网孔站调制器54和电路50,数据链路被用来进行对MTSO(图8)的信号的收与发的通信。
移动单元发射的信号是直接序列扩展频谱信号,该信号由一个以一预定速率定时的PN序列所调制,在最佳的实施例中,该预定速率是1.2288MHz。这一时钟速率被选择为基带数据速率9.6K比特/秒(Kbps)的一个整数倍。
天线30接收的信号送到模拟接收器32。接收器32的细节由图3进一步说明。天线30接收的信号还被送到包含有RF放大器102和混频器104的下行变频器100。所接收的信号被作为RF放大器的输入信号,被其放大并输入到混频器104。混频器104的另一个输入信号是频率同步器106的输出信号。通过与频率同步器输出信号的混频,放大的RF信号在混频器中被移位到一个IF频率。
IF信号从混频器104输出到一带通滤波器BPF108,典型地,为一个1.25MHz通带的声表面滤波器,在其中,IF信号被带通滤波。该滤波的信号从BPF108输出到IF放大器110,在那里,信号被放大。放大的IF信号从IF放大器110输出到一个模-数(A/D)传换器112,在其中,该信号被以恰为8倍PN时隙的速度,即9.8304MHz时钟数率进行数字化。虽然图中表示(A/D)转换器112是接收器32的一个部分,但它也可以是数据与搜索器接收器的一部分。这数字化的IF信号从(A/D)转换器112输出到数据接收器36,可选用的数据接收器38和搜索器接收器34。从接收器32输出的信号是后面将要讨论的I和Q信道信号。虽然在图3中A/D转换器112是一单一装置,具有后置的I与Q信道的信号分离,可以想象到,这种信道的分离也可以在数字化之前来完成,随后利用两个分别的A/D转换器对I与Q信道数字化。对RF-IF-基带频率的下行变频和对I、Q信道的模-数转换器,在本专业技术领域中是公知的。
搜索器接收器34通常用来在网孔站中对所接收的信号的时域扫描,以保证相关的数字数据接收器36、数据接收器38(如被采用的话)在跟踪并处理可获得的最强的时域信号。搜索器接收器64提供一个信号到网孔站控制处理器48,控制处理器48提供控制信号到数字数据接收器36和38以便选择要处理的合适的接收信号。
在网孔站数据接收器和搜索器接收器中的信号处理在几个方面不同于移动单元中类似部件所进行的信号处理。在入界方向,即倒置的或移动-网孔链路方向,移动单元并不发射一个导频信号,该导频信号在网孔站的信号处理中可被用作相关参考的目的。移动-网孔链路的特征在于它采用64状态正交信号(64-ary)。
在64状态正交信号处理中,移动单元发射的码元被编码成26(即64)个不同的二进制序列之一。序列系列的选择被视为沃尔什函数。对于沃尔什函数m状态信号编码的最佳接收函数是快速哈德马得(Hadamard)变换(FHT)。
再来参考图2,搜索器接收器34和数字数据接收器36和38接收从模拟接收器32输出信号。为解码发射到特定网孔站接收器的扩展频谱信号(借助该信号移动单元进行通信),必须产生合适的PN序列。关于该移动单元信号的产生细节将在后面讨论。
如图3所示,接收器36包含两个PN产生器,120和122,它们产生出两个相同长度的不同短码PN序列。就调制方案的外部码而言,这两个PN序列对于全部网孔站接收机和全部移动单元是共同的。所述的调制方案下面还要详述。因此,PN产生器120和122分别提供出序列PNI和PNQ。PNI和PNQ序列分别地被参考作为同相(I)和正交(Q)信道PN序列。
PNI和PNQ序列由不同的15阶多项式产生,被扩大以产生长度为32768的序列而不是通常的32767的长度。比如说,扩增可以用附加一个0到一列14个0的行中,这种14个0的行在每个最大的15阶线性序列中出现一次。换句话说,在产生该序列中,PN产生器的一种状态将被重复。因此,这改进的序列包含有一列15个1和1列15个0。这样的一个PN产生器电路已由正在受理中的美国专利申请“采用快速移位调整的两种长度伪噪声序列产生器的功率”所公开。(流水号071_,申请日_),并受让于本发明的受让人。
在这一实施例中,接收器36还包括一个长码PN产生器124,相对于在移动一网孔链路中移动单元产生的一个PN序列,该产生器124产生出一个PNU序列。PN序列产生器124可为一个最大线性序列产生器,它产生出相当长的(如42阶)用户PN码,且根据一附加因数时间移位,该附加因数如移动单元地址或用户ID,以便在用户中提供识别。因此,网孔站接收的信号既用长码PNU序列调制又用短码PNI和PNQ序列调制。在这种替代中,可以采用一个非线性加密产生器而替代PN序列产生器124,比如说采用一个利用数据加密标准(DES)的加密器,利用一个用户特定键来加密一个64符号世界时间的表示法。
从PN序列产生器124输出的PNU序列与PNI和PNQ序列在异-或门126和128中分别地进行异或操作而生成PNI′和PNQ′序列。
PNI′序列和PNQ′序列连同从接收机32输出的I和Q信道信号一起被送到PN QPSK相关器130。相关器130是用来将I和Q信道数据以及PNI′和PNQ′序列进行相关化的,相关器130输出的相关I和Q信道输出分别送到累加器132和134,在132和134中,这符号数据被积累超过4片周期。累加器132和134的输出送到FHT处理器136。FHT处理器148产生一组对于每6个符号的64个因素。这64个因素再被一个在控制器48中产生的一个加权函数来乘。该加权函数与解调的信号强度相联系。被加权的数据从FHT136输出并被分集相加器和解码器电路(图2)以进一步处理。
第二个接收机系统处理所接收信号的方式与参照图2和图3所讨论的第一个接收系统的方式相类似。从接收器36和46输出的64个加权的符号被送到一分集结合器和解码器电路40。电路50包括一个加法器用来对从接收机36输出的加权的64个因数和从接收机46输出的加权的64个因数相加。这生成的64个因数彼此间相与比较,以便确定其这最大的因数。这种比较的幅值连同其等同或这64个因数的最大值用来确定一组解码器加权值和码元以使用在位于电路50中的Viterbi算法解码器。
电路50中的Viterbi解码器是一种可用来对在移动单元中具有限制长度K=9、码率r= 1/3 的数据编码进行解码的解码器。Viterbi解码器用来确定该最可能的信息比特序列长度。周期地(比如说1.25ms)获得一信号质量的估价,并连同数据一起作为一个移动单元功率的调节命令发送到移动单元。进一步关于这种质量估价信息的生成在上述提到的相关申请中有更详细的讨论。这种质量估计是在1.25ms间隔上的信噪比的平均值。
每一个数据接收器跟踪着其正接收的接收数据的定时。这种跟踪是用公知的技术实现的。这种技术是采用稍早地定位参考PN和稍迟的定位参考PN去特关所收到的信号。这两种相关性的差,在无定时错时为零。反之,如果有定时错误,该差则指示出其程度和错误符号,并且接收机的定时被相应地调节。
网孔站还进一步包括有天线62,它耦合到GPS接收机64。天线62从Navstav全球定位卫星导航系统中的卫星接收的信号由GPS接收机处理以产生出世界相关时间(UTC)指示定时信号。GPS接收机64将这些定时信号提供给控制处理器48,以便在前面讨论的网孔站实现定时同步。
在图2中,可选择的数据接收器38可被包括,以实现改善的系统性能。该接收器的结构和原理与接收器36及46的结构和原理相类似。接收机38可用来在网孔站中获得附加的分集模式。这附加的收器本身或与其它附加接收器的结合可跟踪并接收移动单元发射的信号的其它可能延时路径。象接收机38的这种选择附加数据接收机提供有附加的分集模式,在存在有对于多路信号有多种可能性的入口稠密市区的这些网孔站内,这些附加分集模式是非常有用的。
在控制处理器48的控制下,从MTSO来的信号经数据键路52被耦合到合适的发射调制器。在控制处理器48的控制下,发射调制器对要发射到所期移动单元的数据进行扩展频谱调制。对于发射调制器54的结构及操作的细节将在下面参考图4来讨论。
发射调制器54的输出被提供到发射功率控制电路,在控制处理器48的控制下可实现对发射功率的控制。电路56的输出被提供到取和器57,在那里与对准网孔中其它移动单元的发射调制器/发射功率控制电路的输出相加。取和器57的输出送到发射功率放大器电路58,由此输出到天线60以便辐射到网孔服务区中的移动单元。图2还进一步说明了导频/控制信道产生器和发射功率控制电路66。在控制处理器的控制下,电路66产生并功率控制导频信号,同步信道,和用于耦合至电路58并输出至天线60的寻呼信道。
网孔站发射机的典型实施例的方框图在图4中示出。发射机包括一对用于产生外部码的PN序列产生器。这PN序列产生器,如参考图3所描述的那样,产生两个不同的PN序列,即PNI和PNQ序列。但是,根据区域或网孔地址,PNI和PNQ这两个序列在时间上被延迟。
在图4中,图3中的发射机电路采用导频,同步,寻呼和语音信号使之更为清楚。该发射机电路包括有两个PN产生器,196和198,产生出PNI和PNQ序列。PN产生器196和198响应来自控制处理器的对应于某一区或网孔地址信号的输入信号,以便对PN序列提供预定的延迟。时间延迟的PNI和PNQ序列又分别与同相(I)和正交(Q)信道相关联。对于网孔站或区的相对应信道,虽然只有两个PN产生器被示出来产生PNI和PNQ序列,但是应当理解,许多其它的PN产生器的方案是可行的。比如说,在一个未划分成区的网孔中,对于导频、同步、寻呼和语言信道的每一个都可提供一对PN产生器,以便同步地产生用于外部码的PNI和PNQ序列。这种方案虽说其电路数量庞大,但对于避免干扰PNI和PNQ是有利的。
在这最佳的实施例中采用沃尔什函数编码信道信号作为内部码。如同在此公开的用数字法表示的那样,总共有64种不同的沃尔什序列可采用,而其中三种被用作导频、同步和寻呼信道函数。在同步、寻呼和语音信道,输入数据是卷积编码的并随之被象在本领域熟知的那样交叉。进一步,卷积编码的数据在象本领域熟知那样进行交叉以前,还被重复。
导频信道不包含数据调制,而且其特征是作为一个某特定网孔站或区使用的全部用户的已调扩展频谱信号,用于查询或跟踪的目的。每一个网孔,或分成区的每一个区,都具有独有的一个导频信号。然而,对于这些导频信号不是使用不同的PN产生器,而是象已认识到的那样,是采用移位同一基础序列来生成不同的导频信号这样一种更为有效的方式。采用这种技术的一个移动单元顺序地搜索整个序列并调向产生该最强相关的移位。在采用这种基本序列的位移中,移位必须是:相邻网孔或区的导频必须不干扰或取消。
因而,导频序列必须是足够长,以便利用在基本序列中的移位来产生出许多的不同序列去支持系统中的大量的导频信号。进一步,这种分离或移位必须足够大,以保证在不同导频信号间无干扰。因此,在本发明的一典型实施例中,导频序列的长度选择215。该序列是用生成为215-1的一个序列,当一特定状态被检测到时再附加其上一个额外的0而成的。在典型的实施例中,采用了在基础序列64片的移位的512个不同的导频信号。然而,对应于不同导频信号在数量上的减少,位移可以是64片位移的整数倍。
在该导频信号的产生中,由全零构成的沃尔什“零”序列(Wo)的采用是为了不对本质上为PNI和PNQ的导频信号调制。因而,沃尔什零序列(Wo)在异或门中与PNI和PNQ相乘。这样生成的导频信号就只包含PNI和PNQ序列。而所有的网孔站和区具有相同的PN序列作为导频信号,因此,在原始发射网孔站或区之间的区别特征是该序列的相位差。
对于导频信道的发送调制器和功率控制电路66,沃尔什(Walsh)发生器(Wo)200产生一个相应于刚刚描述的全零函数。Walsh函数产生的定时是由控制处理器提供的,如在网孔站和移动单元中所有Walsh函数发生器的情况。发生器200的输出作为输入提供给异或门202和204。异或门202的其它输入端接收PNI信号,而异或门204的其它输入端接收PNQ信号。PNI和PNQ信号分别与发生器200的输出异或,并分别作为输入提供给有限脉冲响应(FIR)滤波器206和208。从FIR滤波器206和208输出的滤波信号送给包括增益控制器件210和212的发送功率控制电路。给增益控制器件210和212的信号响应从控制处理器来的输入信号(未示出)而被增益控制。从增益控制器件输出的信号供给到发送功率放大电路58,其详细构成和功能在下文中描述。
同步信道信息被编码,然后再在多个异或门中用预先指定的Walsh序列相乘。在典型的实施例中,所选的Walsh函数由32个“零”跟着32个“壹”组成的序列(W32)。然后,得到的序列由PNI和PNQ序列在多个异或门中被乘。在典型的实施例中,同步信道数据优选地以限制长度K=9的一个r=1/2的率卷积编码,每个代码符号重复两次。该编码率和限制长度对所有编码前向链路信道是共同的,如同步,寻呼和话音信道。在典型的实施例中,一个移位寄存器的构成使用了代码G1=753(八进制)和G2=561(八进制)两个发生器。在这个优选的实施例中,对于同步信道的符号率是4800SPS,即一个符号是208微秒或256个PN片。
代码符号借助卷积交错器在实施例中以40毫秒(mS)的间距被交错。交错器的暂定参数是I=16和J=48。交错方向更详细的情况参见“数据通信的网络与系统”Howard  W.Sams  &  Co.,1987  PP.343-352。卷积交错器的作用是分散不可靠的信道符号,以致于在I-1或少许符号的一个相邻序列中,任何两个符号在去交错器的输出中至少被J+1个符号所分开。同样,在J-1个符号相邻近的序列中的任意两个符号,至少被交错器输出的I+1个符号所公开。换句话说,在一串15个符号中,如果I=16及J=48,那么这些符号用885微秒分离传送,以此提供时间分集。
一个特定的网孔或区的同步信道符号被连结那个网孔或区相应的导频信号中。图5表示用64个片移位分离的两个不同导频信道(N)和(N+1)的定时。图5仅代表具有实际导频信号片状态的导频和同步信道定时图的例子,并没有示出同步信道符号。用代码符号对(CX,CX′)的第一个代码符号(CX)表示各同步信道开始一个新的交错周期,由于一个代码重复两次,由等于相导频的量对绝对时间移位。
如图5中所示,在时间tX,N导频信道开始一个新的交错周期或导频同步。类似地,在时间tX产生64片后ty时间,N+1导频信道开始一个新的交错周期或导频同步。在典型的实施例中,导频周期是26.67毫秒,其长度相当于128个同步信道符号或32个同步信道信息比特。同步信息符号由跨度为26.67毫秒的卷积交错器进行交错。于是当移动单元已经获得导频信号时,它同时也与同步信道交错器同步。
同步信道符号由预先分配的Walsh序列所覆盖,以在信号中提供正交性。在同步信道中,一个代码符号横跨4个覆盖序列,即,如图6中所示的,一个代码符号对四个“32个1”-“32个0”相重复的序列。如图6所示,一个单个的逻辑“1”表示32个“1”Walsh片的产生,而一个单个的逻辑“0”则表示32个“0”Walsh片的产生。尽管同步信道符号对取次于导频信道的绝对时间是斜交(skewed),但同步信道中的正交仍被保持,这是因为同步信道位移是Walsh帧的整数倍。
在这个典型的实施例中,同步信道信息的长度是可变的。信息长度是相应于3个导频周期的80毫秒的整数倍。包含同步信道信息的比特采用循环冗余码(CRC)比特,以供误码检测。
图7以定时图的形式表示全部典型的系统定时。在这两秒期间,有75个导频周期。在图7中,N导频和同步信道对应于使用非位移导频的区或网孔,以便导频和同步信号与UTC时间精确地校准。这样的导频同步,如初始状态,用一个公共的每秒1个脉冲(PPS)的信号精确的校准。
总之,在使用移位导频的情况下,插入3相应于导频位移的PN相位偏移。换句话说,导频同步(初始状态)和同步信道信息与1pps信号是斜交的。同步信息带着这个相位偏移信息,以便移动单元能够相应地调整它的定时。
当一个同步信道信息一被正确地收到以后,移动单元立即就有能力与寻呼信道和话音信道进行同步。在相应于各同步信息未端的导频同步点,开始一个新的40毫秒交错周期。那时,移动单元用完成的译码器同步开始去除代码重复或一个(CX,CX+1)对的第一个代码符号的交错。去交错器写地址开始于0并且该地址开始于J,至此存储器去交错器的同步被完成。
同步信道信息携带着用于为移动单元通信指定的话音信道的42一比特长PN发生器状态的信息。该信息用于移动单元数字数据接收机,以同步相应的PN发生器。例如,图7中的同步信道信息N+1包括一个指示状态的42比特信息组,该状态X相应于长码PN发生器的区或网孔话音信道将具有一个预定的稍后时间,例如滞后160毫秒(mS)。在成功的译出同步信道信息之后,移动单元用状态X加载在长码PN发生器的正确时刻。于是移动单元长码PN发生器被同步,以允许预期的用户信息解除扰频。
对用于同步信道的发送调制器和功率控制电路66部分,同步信道信息从控制处理器输入给编码器214。如上面所讨论的,在这个典型的实施例中,同步信道数据由编码器214卷积编码。编码器214进一步还提供重复的已编码符号,在同步信道的情况下,该已编码符号被重复。从编码器214输出的符号提供给用于符号卷积交错的交错器215。交错器215输出的已交错的符号作为输入提供给异或门216。
Walsh发生器218产生一个相应于提供作为异或门216其它输入的Walsh(W32)序列的信号。同步信道符号流和Walsh(W32)序列由异或门216异或,其结果作为输入供给异或门220和222。
异或门222的其它输入端接收PNQ信号,而异或门220的其它输入端接收PNI信号。PNI和PNQ分别与异或门218的输出异或,并分别作为输入供给有限脉冲响应(FIR)滤波器224和226。从FIR滤波器224和226输出的滤波信号提供给包括数字可变增益控制器件228和230发送功率控制电路。提供给增益控制器件228和230的信号响应从控制处理器来的输入数字信号(未示出)数字化地增益控制。从增益控制器件输出的信号提供给发送功率放大器电路58。
寻呼信道信息也被重复编码,交错,然后用预先指定的Walsh序列相乘。得到的序列再由PNI和PNQ序列相乘。对一个特别的区或网孔的寻呼信道的数据速率,在同步信道信息中,以一个指定的字段来表示。虽然寻呼信道数据速率是可变的,但在典型的实施例中,对每个系统来说它是固定的,比如是下面典型数据速率之一;9.6,4.8,2.4和1.2K比特/秒
响应于寻呼信道的发送调制器和功率控制电路,寻呼信道信息是从控制处理器输入到编码器232。在典型的实施例中,编码器232是卷积编码器,它也按照信道的指定数据速率重复提供码元。编码器232的输出供给到交错器233,在那里符号被卷积交错。交错器233的输出作为输入供到异或门234。虽然寻呼信道数据速率将改变,代码符号速率由代码重复保持固定在19.2K样值/秒(SPS)。
Walsh发生器236产生一个响应于预先指定的Walsh序列信号,它作为其它输入供给到异或门234。符号数据和Walsh序列由异或门234异或并作为输入供给到异或门238和240。
当异或门240的其它输入端接收PNQ信号时,异或门238的其它输入端接收PNI信号。PNI和PNQ信号分别地由异或门234的输出异或并且分别地作为输入提供到有限脉冲响应(FIR)滤波器242和244。从242和244输出的滤波信号提供到包括增益控制器件246和248的发送功率控制电路。提供到增益控制器件246和248的信号为响应从控制处理器输入信号(未示出)被增益控制。从增益控制器件输出的信号提供到发送功率放大电路58。
每个声音信道的数据也由它的指定的Walsh序列(Wi-Wj)重复编码、交错、扰频、相乘,然后由PNI和PNQ序列相乘。由特定信道使用的Walsh序列是系统控制器在呼叫建立时,以相同于在模拟FM蜂窝系统中呼叫的信道分配方法进行分配的。在本典型的实施例中,声音信道可用61种不同的Walsh序列。
在本发明典型的实施例中,话音信道使用一个可变的数据速率。当没有话音工作时,使用的可变数据速率的目的是要降低该数据速率而降低该特定话音信道对其它用户的干扰。想象提供可变数字速率的声码器已在悬而未决的美国专利申请“可变速率声码器”中披露,其编号NO_,申请日_,该申请也受让给本发明的受让人。这样的声码器基于声音工作在20mS帧的基础上,能产生四种不同速率的数据。典型的数据速率是9.6千比特/秒(Kbps),4.8Kbps,2.4Kbps和1.2Kbps。虽然数据速率将在20mS的基础上变化,但是代码符号速率由代码重复保持固定在19.2Kbps。因此,各数据速率为4.8Kbps,2.4Kbps和1.2Kbps时,代码符号重复2,4和8次。
因为可变速率的设计要降低干扰,因此,在较低速率的代码符号将具有较低的能量。例如,在典型数据速率为9.6Kbps,4.8Kpbs,2.4Kpbs和1.2Kpbs时,代码符号能量(Es)分别是Eb/2,Eb/4,Eb/8和Eb/16,在此,Eb是9.6Kbps发送速率时的信息比特能量。
代码符号由卷积交错器交错,以致于具有不同能量级的代码符号由交错器的操作产生扰频。为了保持能量的痕迹,将有标号的代码符号附加于用于定标目的指定数据速率的每个符号。在PN扩展和正交Walsh覆盖之后,正交信息被有限脉冲响应(FIR)滤波器滤波。为完成根据数据速率的能量定标,FIR滤波器将接收一个对应于符号的能量级的信号。I和Q信道将由系数:1,1/
Figure 911053158_IMG5
,1/2,或 1/2
Figure 911053158_IMG5
定标。在执行中,声码器以2比特数字形式向FIR滤波器提供速率标记,以控制滤波器的定标系数。
在图4中,表示了两个典型的话音信道(i)和(j)。话音信道(i)的数据是从关联的声码器(未示出)输入到发送调制器54(图3)的。发送调制器54包括偏码器250i;交错器251i;异或门252i,255i,256i和258i;PN发生器253i;和Walsh产生器(Wl)254i。
声音信道(i)数据输入到编码器250i,在典型实施例中,它根据输入数据速率由代码符号重复被卷积编码。在典型实施例中,已编码的数据提供到交错器251i,在那里它被卷积编码。交错器251i也从声码器接收与声音信道(i)有关的2-比特数据速率标记,它与符号数据相交错,对FIR滤波器以该数据速率识别。数据速率标记不发送。在移动装置上,译码器对所有可能的代码进行校验。已交错的符号数据在典型实施例的19.2Ksps速率从交错器251i输出到异或门252i的输入。
在典型的实施例中,每个声音信道信号被扰频以在网孔到移动传送中提供更大的安全。虽然这样的扰频是不需要的,但它在通信中提高了安全。例如,声音信道信号的扰频可由PN代码声音信道信号来完成,PN代码由用户ID的移动装置地址来决定。如参考图3的讨论,相对可移动到网孔通信的特定接收机,这样的扰频可使用PNU序列或加密的方案。因此,一种对这种函数的分离的PN发生器可以实现,正如在图4中表示的那样。虽然扰频在PN序列方面已讨论过扰频也可由包括在现有技术中已知的其他技术来完成。
再参见图4,声音信道(i)信号的扰频可由提供的PN发生器253i完成,发生器253i从控制处理器接收指定的移动装置地址。PN发生器253i产生一个单值的PN代码,它作为其它输入供给到异或门252i。异或门252i的输出当作供给到异或门255i的一个输入端。
响应函数选择信号和从控制处理器来的时间信号,Walsh发生器(Wi)254i产生一个响应于指定的Walsh序列的信号。函数选择信号的值可由移动装置的地址决定。Walsh序列作为其它输入供给到异或门255i。扰频符号数据和Walsh序列由异或门255i异或,其结果作为输入提供到异或门256i和258i这两个的输入端。PN发生器253i与所有其它PN发生器和Walsh发生器一起在网孔站上,在1.2288MHz上提供输出。PN发生器253包括一个十进制器应当注意,它以19.2KHz速率提供输出到异或门255i。
当异或门258i的其它输入端接收PNQ信号时,异或门256i的其它输入端接收PNI信号。PNI和PNQ信号分别地由异或门252i异或并分别地作为输入提供到限制脉冲响应(FIR)滤波器260i和262i。输入符号依照从卷积交错器251i来的输入数据速率标号(未示出)滤波。从FIR滤波器260i和262i输出的滤波信号,供给到包括增益控制器件264i和266i的发送功率控制电路56。供给到增益控制器件264i和266i的信号为响应于从控制处理器来的输入信号(未示出)被增益控制。从增益控制器件输出的信号供给到发送功率放大电路58。
除声音比特以外,正向链路声音信道携带功率控制信息。在典型的实施例中,功率控制比特速率是800bps。从给定的移动中解调移动到网孔信号的网孔站接收机产生功率控制信息,该信息插入到网孔到移动声音信道中,寻找特别的移动的地址。关于功率控制更详细的特征,在上面的悬而未决的申请中已披露。
功率控制比特借助所谓代码符号穿破技术插入在卷积交错的输出。换句话说,每当功率控制比特需要发送两个代码符号总是由功率控制信息给出两个极性完全相同的代码符号代替。此外,功率控制比特是在相应于9600bps比特率的能量级上发送。
强加在功率控制信息流上的附加抑制是比特的位置必需在移动到网孔信道中形成不规则的分布。否则全部的功率控制比特能量将规则交错的产生干扰的脉冲尖峰,于是就减小了这样比特的可检测性。
图4进一步表示在功能和结构方面与声音信道(i)相等的声音信道(i)。可以看出存在有许多的声音信道(未示出),对所说明的实施例声音信道多达61个。
相对于图4的Walsh发生器,Walsh函数是一族正交二进制序列,它能容易地由在现有技术中已知的装置来产生。在Walsh函数中感兴趣的特性是64序列的每一个都完全地与其它所有的序列正交。因此,任何序列对当它们符合时,其比特位置精确性不同,如在一个64符号交错上的32。因此,当信息由Walsh序列编码用于传送时,接收机如要求“载波”信号那样,将能选择Walsh序列的任何一个。已编码进入到其它Walsh序列的任何信号能量将被抑制并对所要求的一个Walsh序列不会引起相互的干扰。
对网孔到移动环的典型实施例中,如前面讲到的,同步、寻呼和声音信道使用限制长度K=9和代码速率r=1/2的卷积编码,就是说,为了传送每一个信息比特要产生并传送两个已编码的符号。除卷积编码外,更进一步使用符号的卷积。重复与卷积编码共同被利用是更进一步预见的。对移动装置,用于这种代码的类型最佳的译码器是软判定Viterbi算法译码器。一种标准的设计能用于译码的用途。已译码信息比特的结果送到移动单元数字基带装置。
再参见图4,电路58包括一组用于变换数字信息的数字/模拟(D/A)变换器,用于把导频,同步,寻呼和话音信道的PNI和PNQ扩展数据变换为模拟形式。特别是导频信道PNI扩展数据是从增益控制器件210输出到D/A变换器268。已数字化的数据是从D/A变换器268输出到加法器284。类似地,用于同步、寻呼和声音信道PNI扩展数据的相应增益控制器件的输出,即增益控制器件228、246和264i-264j,分别地供给到D/A变换器272、276和280i-280j,在此,信号被数字化并供给到加法器284。用于导频、同步、寻呼和声音信道的PNQ分散数据从增益控制器件221、230、248,和266i-266j输出分别地供给到D/A变换器270,274,278和182i-282j,在此,信号被数字化并供给到加法器286。
加法器284计算PNI扩展数据的总数,以用于导频、同步、寻呼和声音信道,与此同时加法器286也在为相同的信道计算PNQ扩展数据的总数。已总计后的I和Q信道数据分别地与本地振荡(LO)频率信号Sin(2πft)和Cos(2πft)一起输入到混频器288和290,在那,它们混频并供给到加法器292。LO频率信号Sin(2πft)和Cos(2πft)由适当的频率源(未示出)提供。这些混频的IF信号在加法器292中相加并供到混频器294。
混频器294将相加后的信号与由频率合成器296提供的RF频率信号混频,以便给RF频带提供频率不变换的信号。从混频器294输出的RF信号由带通滤波器298带通滤波并输出到RF放大器299。放大器299按照从发送功率控制电路56(图3)来的输入增益控制信号放大限带信号。有一点是应该知道的,就是用于说明发送功率放大电路58的实施例,在信号相加、混频、滤波和放大中可能有许多种变化,这种变化如在现有技术中已知的那样。
网孔站控制处理器48(图3)具有指定数字数据接收机和发送调制器到一个特别呼叫的职责。控制处理器48也监视呼叫的进行、信号的品质以及开始信号损耗的拆卸。网孔站经过链路52与MTSO通信,在此,它由标准电话线、光纤、或微波链路连接。
图8以方块图的形式说明在MTSO中使用的装置。MTSO典型地包括一个系统控制器或控制处理器300、数字开关302、分集组合器304、数字声码器306和数字开关308。虽然没有说明附加的分集组合器和数字声码器在数字开关302和308之间的耦合。
当网孔一分集模式工作时,呼叫由两个网孔站处理。因此,信号将从多于1个网孔站以标准相同信息到达MTSO上。无论如何,因为从移动装置到网孔站在入界或返回方面的衰减和干扰,因此,有一个网孔站来的信号比从其它网孔站来的信号品质更好。
数字开关302用于发送相应于从1个或多个网孔站给定的移动装置的信息流到分集组合器304或从系统控制处理器300来的信号决定的相应的分集组合器。当系统不是网孔分集模式时,分集组合器304可被旁路或在每个输入部分馈送相同的信息。
串联耦合分集组合器和声码器的复用以并联供给每个被处理呼叫标准的一个。分集组合物304比较伴随从两个或更多的网孔站信号来的信息比特的信号品质指示器。分集组合304在信息帧到帧的基础上选择相应的最高品质网孔站输出到声码器306。
声码器306将数字声信号的格式变换到标准的64Kbps  PCM电话格式、模拟、或任何其它标准格式。合成的信号从声码器306发送到数字开关308。在系统控制处理器300的控制下,呼叫发送到PSTN。
从打算用于移动装置的PSTN来的声信号,供给到数字开关308,用作耦合到适当的数字声码器,比如在系统控制处理器300的控制下的声码器306。声码器306编码已数字化的声输入信号并直接提供合成信息比特流到数字开关302。在系统控制处理器控制下的数字开关302把已编码数据朝向网孔站或网孔站到正通信的移动装置。虽然在以前讨论的发送到MTSO模拟声音信息,这就预见在系统中,也能够数字信息通信。为保证与系统的兼容性,注意必需采用数据固有的帧。
如果移动装置是以过界切换(hnndoff)模式与多重网孔站通信或者是以网孔分集模式,那么数字开关302发送呼叫到适当的网孔站,以用于由适当的网孔站发送器发送到期望接收的移动装置。无论如何,如果移动装置仅与单个的网孔站通信或不是以网孔分集模式,那么信号仅指向单个的网孔站。
系统控制处理器300提供上面的控制数字开关302或306,用于发送数据到MTSO并从MTSO送出数据。系统控制处理器300也决定到网孔站和到MTSO的声码器呼叫的分配。此外,系统控制处理器300与每个网孔站通信,以便对在MTSO和网孔站之间的特别呼叫分配,及用于呼叫PN代码的分配。应当进一步知道的,如图8中表明的数字开关302和306是由两个分离的开关表示的,无论如何,该功能可由单个实际的开关单元完成。
当使用网孔分集模式时,移动装置将用于搜寻接收以识别和获得从两个网孔站的每一个来的最强的多路径信号。数字数据接收机将由搜寻接收机和控制处理器控制,以便解调最强的信号。当接收机的数量少于以并联发送信息的网孔站数量时,开关分集能力是可以做到。例如,由仅仅单个数据接收机和由两个网孔站发送时,搜寻器将不但监视从网孔站来的导频而且选择最强的信号用于接收机解调。在这实施例中,如每个声码器帧或大约每20mS的频繁次数的选择是可以做到的。
系统控制处理器已对数字数据接收的分配和在网孔站处理特别的呼叫负起责任。因此,在网孔到移动链路中,系统控制处理器控制使用在网孔站个别呼叫到移动装置的发送中的Walsh序列的分配。此外,系统控制处理器控制接收Walsh序列和PN代码。在移动到网孔链路中,系统控制处理器也控制呼叫的移动装置用户PN代码。为此,分配信息是从MTSO到网孔站发送并且从那里到网孔,到移动。系统控制处理器也监视呼叫的进行、信号的品质、和开始卸下信号的损耗。
移动到网孔链路
在移动到网孔链路中,信道特征指令,其调制技术将被改进。特别地,如使用在网孔到移动链路中的导频载波的使用是决不行的。为了给数据调制提供好的相位参考,导频载波必须比声音载波强。由于网孔站的发送许多同时发生的声音载波,一个单个导频信号能被所有话音载波分担。因此,每个话音载波的导频信号功率是很小的。
在移动到网孔环中,无论如何,经常是每个移动仅有一个话音载波。如果使用导频,重要的是要求功率大于话音载波。这种情况很清楚是不理想的,因为所有系统容量将大大缩小,这是由于存在大量高功率导频信号引起干扰的原因。因此,必需使用一种没有导频信有效解调的有能力的调制。
由(Rayleigh)雷利衰减使移动到网孔信道的恶化,结果是迅速改变信道相位、相干码解调技术、比如从接收的信号得到相位的Dostas环路,这是不可行的。其它的技术,比如,差动相干的PSK能够使用,但它不能提供所需的信号/噪声比电平。
因此,一种如二进制、四进制或m-状态(ary)信号的正交信号的形式将被使用。在典型的实施例中,一种64-ary正交信号技术被用于Walsh函数。对m-ary正交信号的解调器要求信道相干仅在发送m-ary符号的持续时间上,在典型的实施例中,这仅是两比特时间。
信息编码和调制处理从限制长度K=9和代码率r=1/3的卷积编码开始。以每秒9600比特的标称数据速率,偏码器每秒产生28800个二进制符号。它们被组合为包括6个符号的字符,每个以每秒4800个字符的速率,具有64个可能的字符。每个字符被编码进包括64个二进制比特或“片”的一个长64的Walsh序列。在典型的实施例中,64-ary  Walsh片速率是每秒307200片。
然后,Walsh片被“复盖”或被以1.2288MHz的速率运行的PN序列相乘。为了这个目的,每个移动装置分配一个单值PN序列。这种PN序列仅被分配用于呼叫的持续,或对移动装置永久地分配。分配的PN序列参见这里的用户PN序列。用户PN序列发生器工作在1.2288MHz的时钟速率上,以便产生4个PN片,以用于每个Walsh片。
最后,发生了一对短的,长度为32768的PN序列。在典型的实施例中,相同的序列用作网孔到移动链路。然后复盖Walsh片序列的用户PN序列被复盖或被两个短PN序列中的每个相乘。然后,两个得到的序列双相位调制正弦曲线的正交对并相加成为一个单个信号。然后,所得信号被带通滤波、变为最后的RF频率、被放大、滤波并由移动装置的天线辐射。参考网孔到移动信号的讨论,滤波的顺序、放大、传送和调制操作可以被互换。
在替代的实施例中,可产生用户PN代码的两个不同相位并用于调制正交相位波形的两个载波相位,免去使用32768序列长度的必要。还在其它的替代中,移动到网孔链路仅使用双相位调制,也免去短序列的需要。
网孔站接收机对每个信号产生短PN序列而用户PN序列对每个工作的移动信号进行接收。接收机使接收的信号能量与在分离相关器中每一个代码波形发生联系。然后,相关器的每个输出分离地处理去解调64-ary编码以及用快速Hadamard变换处理器和Viterbi算法译码器的卷积代码。
在另外的用于移动到网孔链路的替代调制方案中,相同的调制方案将用于网孔到移动链路。每个移动将利用一对32768长度区代码作为外部代码。当它在那个区时,内部代部将利用分配到供移动使用的长64Walsh序列。名义上,相同的Walsh序列将被分配到移动,对于移动到网孔链路就象对于网孔到移动链路一样。
上面的正交PN代码方案限定可能得到的带宽扩展,上面的方案由调制系统用于被64除的片率的最大的速率,或者是典型的实施例中的19200Hz。这就排除使用具有大的m的m-ary编码,正如典型实施例描述的那样。作为替代,无论如何,速率r=1/2、限制长度K=9卷积代码将与已编码二进制符号的差分二进制相移键控调制一起使用。在网孔站中的解调器建立一个利用论文中描述的技术的一个短间隔的相位参考,该论文是“应用于猝发数字发送的PSK-调制载波的非线性评价”,Andrew  J.Viterbi和Audrey  M.Viterbi,IEEE信息发送原理,Vol  IT-29,No.4,1983.7。例如,一个相位参考在所要求信道相干不多于上面的64-ary方案时,仅平均是4个符号。
刚描述的替代方案的性能,在存在急剧的雷利Rayleigh衰减和多路径情况下,无论如何,都将次于优选的实施例。然而,在确定的环境,即衰减和多路径都急剧小的情况下,例如,卫星移动信道和确定的地面移动信道,替代系统的性能将比优选的实施例好。这种情况是能产生的,因为,使移动信号互相正交的增益超过了DPSK方案的检测效率的损耗。
为了满足用于替代的移动到网孔环的Walsh函数在校准正交方面所必需的时间,每个网孔从每个接收信号的标称时间决定时间误差。如果给出的接收信号时间滞后,那么相关联的网孔调制器和发送器将发送一个指令到这个移动装置,用小的增加推进它的发送时间。相反地,如果移动装置接收信号时间超前标称时间,用小的增加延迟的指令发送到移动装置。时间校准增量大约1/8PN片或101.7毫微秒。指令在相对低的速率上发送,大约10到50Hz以及由插到数字话音数据流的信号比特组成。
在软过界切换操作期间,移动装置将从两个或多个网孔接收信号。因为移动装置仅能响应网孔时间校准指令的一个来校准它的时间,移动装置将正常地随着从最强的网孔接收到的指令移动它的时间。于是,发送信号的移动装置将用网孔具有的最好的路径来校准时间。否则,对其它的用户将引起较大的相互干扰。
如果接收移动信号的每个网孔接收机完成上面的时间误差测量并校正发送操作,然后,接收信号的所有移动装置将正常地接收大致相同的定时,其结果是减小了干扰。
图9以方框图形式表示一个典型的移动装置CDMA电话机。移动装置CDMA电话机包括一个经过双工器432耦合到模拟接收机344和发送功率放大器436的天线430。天线430和双工器432是按标准设计并允许经过单独的天线同时发送和接收。天线430收集发送信号并经过双工器432把它们供给到模拟接收机434。接收机434从双工器432接收RF频率信号,双工器432典型地工作在850MHz频带,用于放大和频率下变到IF频率。传送过程是用标准设计的频率合成器完成,允许接收机调谐到在所有蜂窝电话接收频带之内的任何频率。信号也被滤波和数字从用来提供到与搜索接收机544一起的数字数据接收机540和542。
图10更进一步详细说明接收机434。从天线430接收的信号供给到下变换器500,它包括RF放大器502和混频器504。接收到的信号作为输入供给到RF放大器502,在此它们被放大并输出到混频器504的输入。混频器504有其它的输入,输入是从频率合成器506输出的信号。放大的RF信号在混频器504中与频率合成器输出信号混频变换到IF频率。
IF信号从混频器504输出到带通滤波器(BPF)508,典型的表面声波(SAW)滤波器具有大概1.25MHz的带通,在那里它们被带通滤波。SAW滤波器的特性被选择以匹配由网孔站发送的信号的波形。网孔站发送的信号是一个直接序列扩展频谱信号,它以预定速率定时的PN序列调制,在典型实施例中是1.2288MHz,时钟速率被9.6Kbps的基带数据速率整体多重选择。
滤波信号从BPF508输出作为输入到一个可变增益IF放大器510,在此信号再一次放大。放大的IF信号从IF放大器510输出到模拟到数字(A/D)变换器512,在此信号被数字化。在典型实施例中,IF信号到数字信号的变换发生在9.8304MFZ时钟速率上,它正巧是PN片速率的8倍。虽然(A/D)变换器512由接收机534部分表示,但它可被数据和搜索接收机部分代替。数字化的IF信号从(A/D)变换器512输出到数据接收机440和442,以及搜索接收机444。
接收机434也执行调准移动装置的发送功率的功率控制作用。自动增益控制(AGC)电路514也耦合到放大器570的输出。相应于放大IF信号的电平,AGC电路514供给一个反馈信号到IF放大器510的增益控制输入。接收机434也用AGC电路514产生一个模拟功率控制信号,它被供给到发送功率电路438。
在图9中,数字化信号从接收机434输出供给到数字数据接收机440和442和搜寻接收机444。有一点应当是知道的,就是当高性能(移动)装置具有两个或多个接收机以便分集接收,而低性能移动装置仅有单个信号数据接收机,其成本是便宜的。
数字IF信号包括许多正在进行的由现在的网孔站和所有邻近的网孔站用导频载波发送的相互呼叫的信号。接收机440和442的函数是使IF采样与原来的PN序列相关。
该相关过程提供一个在现有技术中已知的特性,如“处理增益”,在不增强其它信号时,它提高了匹配原来PN序列信号的信号对干扰的比率。然后,相关输出用从最接近的网孔站来的导频载波同步检波,作为载波相位参考。检波过程的结果是编码数据符号的一个序列。
用于本发明中的PN序列的特性,它提供相对多路径信号的鉴别。在经过多于1个路径之后,当信号到达接收机时,信号的接收时间将是不同的。这种接收时间的差相应于距离被传播速度除的差。如果时间差超过1个微秒,那么相过程将在路径之间鉴别。接收机能决定跟踪和接收较早的还是较迟的路径。如果提供两个接收机,比如接收机440和442,那么,就能平行的跟踪和处理两个独立的路径。
对从相同的网孔站来的其它多路径导频信号和其它网孔站发送的导频信号在控制处理器446的控制下,搜寻接收机444连续扫描时域网孔站接收的导频信号的标准时间,并用于从相同网孔站来的其它多路径导频信号和其它网孔站发送的导频信号。接收机444有时除标准时间外将测量接收的任何所需波形的强度。接收机444在接收的信号中,比较信号强度。接收机444提供一个信号强度的信号到控制处理器446,以指示最强的信号。
处理器446给数据接收机440和442的每一个提供控制信号,以处理不同信号中最强的一个。有时其它的网孔站发送的导频信号的信号强度大于现在的网孔站信号强度。然后,控制处理器446产生一个控制消息位目前的网孔站传送给系统控制器,请求把网孔转变到相应于最强导频信号的网孔站。因此接收机440和442可以处理通过两个不同网孔站来的呼叫。
在一个软过界切换操作期间,移动装置将从两个或多个网孔接收信号。由于移动装置仅能相应于网孔定时调整命令中的一个去校准它的时间,所以相对于接收的最强网孔的接收指令,移动装置将正常地移动它的时间。于是,发送信号的移动装置将用它具有最好的路径进行时间校准。否则,将引起对其它用户大的相互干扰。
更进一步详细的典型接收机,比如在图10中更详细表示的数据接收机440。数据接收机440包括在某种意义上对应由网孔站产生的那些,产生PNI和PNQ序列的发生器516和518。从控制处理器446来的定时和序列控制信号供给到PN发生器516和518。数据接收机440也包括由网孔站供给合适的Walsh函数用于与移动装置通信的Walsh发生器520。Walsh发生器520产生响应定时信号(未示出)和一个从控制处理器来的函数选择信号,一个与分配的Walsh序列相应的信号。函数选择信号由作为呼叫建立信息部分的网孔站发送到移动单元。从PN发生器516和518输出的PNI和PNQ序列分别地输入到异或门522和524。Walsh发生器520把它的输出供到异或门522和524,在此,信号被异或并输出PN′和PNQ′序列。
序列PNI′和PNQ′提供到接收机440,在那里它们输入到PN QPSK相关器526。PN相关器526可以类似于网孔站数字接收机的PN相关器方式构成。PN相关器526用PNI′和PNQ′序列相关接收I和Q信道数据并把相关的I和Q信道数据输出到相应的累加器528和530。累加器528和530在一个符号或64片的一个周期上累加该输入信息。累加器的输出提供到相位旋转器532,它也从控制处理446接收一个导频相位信号。接收符号数据的相位按照由搜索接收机和控制处理器决定的导频信号的相位来旋转。相位旋转器532的输出是I信道数据,它提供给去间隔器和解码电路。
控制处理器446也包括PN发生器534,它为响应输入移动单元地址或用户ID发生用户PN序列。从PN发生器534输出的PN序列供给到分集组合器和解码电路。因为网孔到移动信号是由移动用户地址PN序列扰频,PN发生器534的输出用于打算使这个移动用户类似于在网孔站接收机中一样的发送信号的网孔站的去扰频。PN发生器534特别地把PN序列输出供到去间隔器和解码电路,在那里,它用于去掉扰频的用户数据。虽然扰频参考PN序列已讨论过,可以想到包括在现有技术中的已知的扰频技术也可以利用。
于是接收机440和442的输出供给到分集组合器和解码电路448。包括在电路448中的分集组合电路简单地调整校准两个接收符号流的定时,并把它们加在一起。这种附加处理可由相对两个流的有关信号强度的数字乘两个流来处理。这种操作可考虑一个最大比率的分集组合器。然后,得到的组合信号流也用包括在电路448中的正向误差检测(FEC)解码器解码。通常数字基带装置是一个数字声码器系统。CDMA系统设计成容纳各种不同的声码器的结构。
基带电路450典型地包括一个数字声码器(未示出),它可以是可变速率型式,如在以前悬而未定的专利申请中披露的那样。基带电路450更用作与手机或任何其它类型的外部装置的接口。基带电路450容纳各种不同的声码器结构。此外,与电路448供给的信息相应的,基带电路450给用户提供输出信息信号。
在移动到网孔链路路中,用户模拟声信号典型地经过手机提供并作为输入送到基带电路450。基带电路450包括一个模拟到数字(A/D)变换器(未示出),它转换模拟信号到数字数字信号供给到数字声码器,在此,它被解码。声码器输出供给到用于误差校正的正向误差校正(FEC)编码电路(未示出)。在典型实施例中,完成的误差校正编码是卷积编码的型式。数字化已编码的信号从基带电路450输出到发送调制器452。
发送调制器452先Walsh编码发送数据,然后在一个PN载波信号上调制已编码信号,PN序列是根据为呼叫分配地址函数决定的。PN序列由从呼叫建立信息的控制处理器446决定,它由网孔站发送并由接收机440和442以及控制处理器446解码。另外,控制处理器446可以由网孔站的预先安排决定PN序列。控制处理器446提供PN序列信息到发送调制器452以及到接收机440和442去用于呼叫解码。
发送调制器452的输出被提供到发送功率控制电路438。信号发送功率由接收机434提供的模拟功率控制信号控制。由功率调整指令形式的网孔站发送的控制比特,由数据接收机440和442处理。功率调整指令在移动单元传送中设置功率电平,它由控制处理器446使用。响应于这个指令,控制处理器446产生一个数字功率控制信号,它被供给到电路438。对于接收机440和442更进一步的信息,关于功率控制方面的控制处理器446和发送功率控制器438,在上面悬而未定的专利申请中,作了进一步的描述。
发送功率控制电路438输出功率控制调制信号到发送功率放大电路436。电路436放大并用一个频率合成器输出信号用混频方式将IF信号变换到RF频率,它把信号调谐到原来的输出频率。电路436包括一个将功率放大到最后输出电平的放大器。预想的发送信号从电路436输出到双工器432。双工器432把信号耦合到天线340,用于发送到网孔站。
控制处理器446也能够产生控制信息,比如网孔-分集模式请求和网孔站通信终端指令。这些指令供给到发送调制器452,用于发送。控制处理器446响应从数据接收机440和442接收的数据以及响应搜寻接收机444做的有关过界切换(hand  off)和分集组合的决定。
关于由移动单元的发送,移动用户模拟声信号首先经过一个数字声码器发送。然后,声码器依次输出卷积正向误差校正(FEC)编码、64-ary正交序列编码并调制在一个PN载波信号上。64-ary正交序列是由Walsh函数编码器产生。编码器由收集从卷积FEC编码器输出6个连续的二进制符号控制。6个二进制总集合就确定有64个Walsh序列被发送的可能。Walsh序列是64比特长。于是,对9600bps数据发送速率Walsh“片”速率必需是96003(1/6)64=307200Hz。
在移动到网孔链路中,当用户地址编码做为用户PN序列发生器时,在系统中一个公共短PN序列被用于所有话音载波。用户PN序列单值地分配到移动单元至少用于呼叫的持续时间。用户PN序列与公共PN序列相异或,它们是增加的最大的线性移位寄存器序列的长度32768。然后所得二进制信号的每个双相位调制一个正交载波、被加为组合信号形式、被带通滤波,最后变换为IF频率输出,在典型实施例中,滤波处理的部分实际地由工作在二进制序列输出上的有限脉冲响应(FIR)数字滤波器完成。
然后,调制器的输出是由数字控制处理器和模拟接收机来的信号功率控制的,用把信号调谐到适当输出频率的频率合成器混频变换到工作的RF频率、然后放大到最后输出电平。然后发送的信号传送到双工器和天线。
图11表示一个优选的但也是典型的移动单元发送调制器452的实施例。数据以数字形式从用户数字基带电路供给到编码器600,在此的典型实施例中是卷积编码。编码器600的输出供给到交错器602,在典型实施例中是数据块交错器。已交错的符号从数据块交错器602输出到发送调制器452的Walsh编码器604。Walsh编码604利用输入符号以产生一个代码序列输出。Walsh序列供给到异或门606的一个输入端。
发送调制器452进一步包括接收移动单元地址的PN发生器608,作为输入以确定输出PN序列。PN发生器608产生用户特定的42比特序列,如参照图3和图4所讨论过的。PN发生器608的进一步属性是所有用户的PN发生器是公共的,以前没有描述过,是利用掩技术(masking)产生输出的用户PN序列。例如,一个42比特掩码提供给用户从构成PN发生器的一组移位寄存器的每个寄存器来的一个比特与42比特异或的各个比特。掩码和移位寄存器比特异或作用的结果然后相互异或以形成PN发生器输出,该输出用作用户PN序列。PN发生器608的输出PN序列,即序列PNU,输入到异或门606。Walsh符号数据和PNU序列在异或门606中异或并作为输入供给到异或门610和612。
发送调制器452进一步包括各自发生PNI和PNQ序列的PN发生器614和616。所有移动单元都使用相同的PNI和PNQ序列。在典型实施例中,这些PN序列是使用在网孔到移位通信中的零位移。异或门610和612另外的输入是从PN序列发生器614和616分别输出的PNI和PNQ序列供给的。PNI和PNQ序列是与供给到发送功率控制器438(图9)的输出在各自的异或门中被异或。
在典型实施例中,移动到网孔链路使用速率r=1/3限制长度K=9卷积代码。用于代码的发生器是G1=557(八进制)、G2=663(八进制)、和G3=711(八进制)。类似于网孔到移动链路,代码重复使用以容纳四个不同的数据速率,数据速率声码器在20毫秒帧基上产生的。与网孔到移动链路不同,在较低能量电平的空间,重复代码符号不发送,相反,仅仅一个重复群组的代码是在标称功率电平上发送。总之,在典型实施例中的代码重复用在交错和调制结构中仅仅作为方便适合于可变数据速率的设计,这一点,如将在下面文章中的说明。
跨距20毫秒,声码器帧的数据块交错器用在移动到网孔链路中。假设一个9600的数据速率和一个代码速率r=1/3,在20毫秒中,代码符号的数目是576。N等于列的数字和B等于交错器排列的行数字,N和B参数分别是32和18。代码符号由行写进交错器存储器以及由列读出。
调制格式是64-ary正交信号。换句话说,交错代码符号被编为六个组,以选择64个正交波形输出中的一个。64次正交波形是相同的Walsh函数,在网孔到移动链路中用作复盖序列。
数据调制时间区间等于208.33微秒,并称为Walsh符号区间。在9600bps时,208.33微秒相当于2个信息比特,并且在一个代码符号速率等于28800sps时,相当于6个代码符号。Walsh符号区间再细分为64个相等长度时间区间,称为Walsh片,每一个持续208.33/64=3.25微秒。然后,Walsh片速率是1/3.25微秒=307.2KHz。因为PN扩展速率在两个链路间即1.2288MHz,是对称的,因此每个Walsh片正巧有4个PN片。
三个PN发生器全都用于移动到网孔链路通路中。用户特定的42比特PN发生器和一对15比特I和Q信道PN发生器。随着用户特定的扩展操作,信号被QPSK扩展,就像它在网孔到移动链路中所做的一样。与网孔到移动环不同,在此每个区或网孔由长度215的单值序列识别,在这里所有移动单元使用相同的I和Q PN序列。这些PN序列是用于网孔到移动链路中的零移动序列,也称为导频序列。
代码重复和能量定标用在网孔到移动链路中,以容纳由声码器产生的可变的速率。移动到网孔链路基于猝发传送使用不同的方案。
声码器如在网孔到移动链路中,在20毫秒帧基础上,产生4个不同的数据速率,即9600、4800、2400、和1200bps。信息比特由速率r=1/3卷积编码器编码并且代码符号在三个较低的数据速率上重复2、4和8次。于是,代码符号速率在28800sps上,保持常数。随着编码器、代码符号被数据块交错器交错,它的跨距正巧是一个声码器帧或20毫秒。每20毫秒由卷积编码器产生总共576个代码符号,其中一些可以是重复符号。
在图12中表示被发送的代码符号序列。注意,一个20mS声码器帧已经被细分为16个时隙,每个时隙持续1.25毫秒。移动到网孔链路的数学(mumerology)是为了在28800sps速率时,每个时隙有36个代码符号或者相等于速率为4800sps的6个Walsh符号。在1/2速率,即4800bps时,间隙被组成每个包括2个时隙的8个组。在1/4速率,即2400bps时,时隙被组成每个包括4个时隙的4个组,最后,在1/8速率,即1200bps时,时隙被组成每个包括8个时隙的2个组。
在图12中进一步表示一个典型符号猝发传送的图形。例如,以1/4速率,即2400bps时,在第一组的第四时隙期间,交错存储器阵列的第四和第八行由列读出并且顺序地发送。发送数据的时隙位置必需形成不规则分布,以减少干扰。
在图13中表明移动到网孔链路的定时。图13阐述了包括移动到网孔信道,即话音和入口的图7的定时图。移动到网孔链路的同步包括下面步骤:
1.成功地解码同步信息,即CRC校验;
2.用在同步信息中接收的状态加载长PN移位寄存器;
3.如果从使用移位的导频的区接收,校正导频代码相位偏移。
这时移动已经完成同步,即PN同步和实时同步,并且能够开始在入口信道或话音信道上发送。
移动单元为了开始呼叫必需具备信号特性,以便经过网孔站完成到另外系统用户的呼叫。在移动到网孔链路中,想象入口技术是有隙的ALOHA。在反向信道上,一个典型的发送比特率是4800bps。一个入口信道信息组包括由信息跟随的前文(preamble)。
前文长度在典型实施例是20mS帧的整倍,它也是在一个寻呼信道信息中该移动接收的一个区/网孔参数。因为网孔接收机使用前文以分辨传播延迟,该方案允许前文长度基于网孔半径的变化。用于入口信道的用户PN代码是预先安排的或是在寻呼信道上发送到移动单元。
对前文的持续时间,调制是固定和不变的。用在前文中的正交波形是W0,即,所有零Walsh函数。注意,在卷积编码的输入上的所有零图形发生所要求的波形W0
一个入口信道数据包可包括一个或至多两个20mS帧。编码、交错、以及入口信道的调制正巧是相同的,如像9600bps速率的话音信道一样。在典型实施例中,区/网孔要求移动单元发送一个40mS前文和要求一个数据帧的入口信道信息类型。令Np是前文帧的数字,在此,K是从预先规定时间起始经过的20mS的数字。然后,仅当方程:(K、Np+2)=0是真实时,移动允许开始在入口信道上发送。
关于其它的通信应用,它可希望预先安排误差校正代码的各种不同的部件、正交序列代码以及PN代码可较好的适合于应用。
例如,在卫星移动通信中,在那里信号在大的Hub地球站和一个或多个地球轨道卫星的移动终端之间中继,它可以要求在链路的两个方向中应用相干调制和解调技术,因为信道更大的可能是相位相干而不是地面的移动信道。在这样的应用中,移动调制器将不利用m-ary偏码,如上面所说的。代之以双相或四相的正向误差校正符号的调制,可以使用科斯特斯(Costas)回路技术接收的信号中提取载波相位用于一般相干解调。另外,如在本文中说明的用于网孔至移动链路的正交Walsh函数的信道化是可以应用的。只要信道相位合理地保持相干,该调制和解调系统就能提供比m-ary正交信号导致的高系统容量更低的Eb/No操作。
在另外的实施例中,更可取的是用直接把话音波形编码为射频(RF)波形取代使用声码器和FEC技术。而使用声码器和FEC技术产生很高的链路性能时,设备的复杂性很高,由此导致附加成本和高的功率消耗。这些缺点不利于小型便携式的电话,在那电池的消耗和成本是很重要的。在通常的数字电话发送传输实践中,话音波形以8KHz取样率取样,以8比特话音样值的数字格式表示。CDMA系统直接将8比特样值编码为载波相位角。这将取消声码器或FEC编码器/解码器的必要。对要求好的性能来说,这也就稍为提高了一点信号对噪的比率,其结果是降低了容量。在另外的方案中,8比特话音样值编码为载波幅度。还在另外的方案中,话音波形样值编码为载波相位和幅度。
前面优选实施例的说明能够提供在现有技术中任何熟练的人制造或使用本发明。这些实施例的各种改进,对现有技术中的这些熟练的人将是容易的、显而易见的,以及在本文中由普通原理限定的可用到没有使用本发明能力的其它实施例。因此,本发明不打算对本文中所表示的实施例进行限制,但是,最宽范围将与在本文中披露原理和新特征相一致。
关于图7和图13的补充说明。在图7和图13中,同步信息有80毫秒倍数的长度,80毫秒等于两个交错(器)周期或4个声码帧。图7中,在时间tSYNC,用户长(42比特)PN发生器处于X状态。且此时在网孔寻呼或话音信道中,长PN发生器为扰频加载X;新比特的第一个代码符号被加载;去交错写地址恢复为0,而读地址恢复为J;且在网孔寻呼或话音信道中开始一个新的交错周期。在图13中,在时间tSYNC,用户长(42比特)PN发生器处于X状态;在网孔寻呼或话音信道中,长PN发生器为扰频加载X新比特的第一个代码符号被加载;去交错写地址恢复为0,而读地址恢复为J;且在网孔寻呼或话音信道中开始一个新的交错周期。另外在上述时间tSYNC,在移动话音信道中,新比特和新WALSH符号的第一码元符号被加载;交错器写地址和读地址恢复到0;且新交错器周期和一个新的声码帧开始。也在时间tSYNC,在移动入口信道中,新比特和新WALSH符号的第一码元符号被加载,且交错器写和读地址恢复到0。

Claims (4)

1、一种用于扩展频谱通信的调制系统,包括:
用于产生一个第一正交序列信号的装置,该信号对应于多个正交二进制序列中所选择的一个;
用于产生一个相应于一个预定PN二进制序列的伪噪声(PN)信号的装置;
用于组合所说的第一正交序列信号和所说的PN信号,并用于提供一个合成的第一调制信号的装置。
2、如权利要求1的系统进一步包括将所说的第一调制信号与一个输入信号组合起来,并用于提供一个合成扩展频谱信息信号的附加装置。
3、如权利要求1的系统,其中所说的多个正交二进制序列是沃尔什(Walsh)序列。
4、如权利要求1的系统,其中所说的PN序列是一个扩大长度的最大线性序列PN码。
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CN1096158C (zh) * 1994-09-30 2002-12-11 夸尔柯姆股份有限公司 在公共信道上对多个波形求和的串联互联接
CN1079615C (zh) * 1995-06-30 2002-02-20 夸尔柯姆股份有限公司 使用多沃尔什信道的码分多址通信系统中的码捕获
CN1321505C (zh) * 1998-03-04 2007-06-13 日本电气株式会社 采用单一扩频码的频谱扩展通信系统
CN1501613B (zh) * 1999-02-26 2010-05-12 高通股份有限公司 Cdma无线通信系统中缩减同步时间的方法和系统
CN100341268C (zh) * 1999-10-04 2007-10-03 摩托罗拉公司 传输呼叫的方法和装置
CN101567756B (zh) * 1999-11-22 2013-03-06 英特尔公司 用于前向链路的变速率编码
CN1902847B (zh) * 2003-12-29 2014-03-05 英特尔公司 用于加扰的位传输的发射器和方法
CN101552751B (zh) * 2009-05-08 2012-06-06 王红星 基于椭圆球面波函数的调制方法
CN103380575A (zh) * 2010-12-21 2013-10-30 法国电信 报警信号检测的保护
CN108259145A (zh) * 2016-12-28 2018-07-06 电信科学技术研究院 一种数据传输方法、发送装置及接收装置
CN111446884A (zh) * 2019-01-17 2020-07-24 佳能株式会社 振动型致动器及振动型致动器的制造方法

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