WO1997018508A1 - Pressure sensitive scrollbar feature - Google Patents
Pressure sensitive scrollbar feature Download PDFInfo
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- WO1997018508A1 WO1997018508A1 PCT/US1996/017862 US9617862W WO9718508A1 WO 1997018508 A1 WO1997018508 A1 WO 1997018508A1 US 9617862 W US9617862 W US 9617862W WO 9718508 A1 WO9718508 A1 WO 9718508A1
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- sensor
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- capacitance
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- G—PHYSICS
- G06—COMPUTING; CALCULATING OR COUNTING
- G06F—ELECTRIC DIGITAL DATA PROCESSING
- G06F3/00—Input arrangements for transferring data to be processed into a form capable of being handled by the computer; Output arrangements for transferring data from processing unit to output unit, e.g. interface arrangements
- G06F3/01—Input arrangements or combined input and output arrangements for interaction between user and computer
- G06F3/048—Interaction techniques based on graphical user interfaces [GUI]
- G06F3/0487—Interaction techniques based on graphical user interfaces [GUI] using specific features provided by the input device, e.g. functions controlled by the rotation of a mouse with dual sensing arrangements, or of the nature of the input device, e.g. tap gestures based on pressure sensed by a digitiser
- G06F3/0488—Interaction techniques based on graphical user interfaces [GUI] using specific features provided by the input device, e.g. functions controlled by the rotation of a mouse with dual sensing arrangements, or of the nature of the input device, e.g. tap gestures based on pressure sensed by a digitiser using a touch-screen or digitiser, e.g. input of commands through traced gestures
-
- G—PHYSICS
- G06—COMPUTING; CALCULATING OR COUNTING
- G06F—ELECTRIC DIGITAL DATA PROCESSING
- G06F3/00—Input arrangements for transferring data to be processed into a form capable of being handled by the computer; Output arrangements for transferring data from processing unit to output unit, e.g. interface arrangements
- G06F3/01—Input arrangements or combined input and output arrangements for interaction between user and computer
- G06F3/048—Interaction techniques based on graphical user interfaces [GUI]
- G06F3/0484—Interaction techniques based on graphical user interfaces [GUI] for the control of specific functions or operations, e.g. selecting or manipulating an object, an image or a displayed text element, setting a parameter value or selecting a range
- G06F3/0485—Scrolling or panning
- G06F3/04855—Interaction with scrollbars
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- G—PHYSICS
- G06—COMPUTING; CALCULATING OR COUNTING
- G06F—ELECTRIC DIGITAL DATA PROCESSING
- G06F3/00—Input arrangements for transferring data to be processed into a form capable of being handled by the computer; Output arrangements for transferring data from processing unit to output unit, e.g. interface arrangements
- G06F3/01—Input arrangements or combined input and output arrangements for interaction between user and computer
- G06F3/03—Arrangements for converting the position or the displacement of a member into a coded form
- G06F3/041—Digitisers, e.g. for touch screens or touch pads, characterised by the transducing means
-
- G—PHYSICS
- G06—COMPUTING; CALCULATING OR COUNTING
- G06F—ELECTRIC DIGITAL DATA PROCESSING
- G06F3/00—Input arrangements for transferring data to be processed into a form capable of being handled by the computer; Output arrangements for transferring data from processing unit to output unit, e.g. interface arrangements
- G06F3/01—Input arrangements or combined input and output arrangements for interaction between user and computer
- G06F3/03—Arrangements for converting the position or the displacement of a member into a coded form
- G06F3/041—Digitisers, e.g. for touch screens or touch pads, characterised by the transducing means
- G06F3/0416—Control or interface arrangements specially adapted for digitisers
-
- G—PHYSICS
- G06—COMPUTING; CALCULATING OR COUNTING
- G06F—ELECTRIC DIGITAL DATA PROCESSING
- G06F3/00—Input arrangements for transferring data to be processed into a form capable of being handled by the computer; Output arrangements for transferring data from processing unit to output unit, e.g. interface arrangements
- G06F3/01—Input arrangements or combined input and output arrangements for interaction between user and computer
- G06F3/03—Arrangements for converting the position or the displacement of a member into a coded form
- G06F3/041—Digitisers, e.g. for touch screens or touch pads, characterised by the transducing means
- G06F3/0416—Control or interface arrangements specially adapted for digitisers
- G06F3/04166—Details of scanning methods, e.g. sampling time, grouping of sub areas or time sharing with display driving
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- G—PHYSICS
- G06—COMPUTING; CALCULATING OR COUNTING
- G06F—ELECTRIC DIGITAL DATA PROCESSING
- G06F3/00—Input arrangements for transferring data to be processed into a form capable of being handled by the computer; Output arrangements for transferring data from processing unit to output unit, e.g. interface arrangements
- G06F3/01—Input arrangements or combined input and output arrangements for interaction between user and computer
- G06F3/03—Arrangements for converting the position or the displacement of a member into a coded form
- G06F3/041—Digitisers, e.g. for touch screens or touch pads, characterised by the transducing means
- G06F3/044—Digitisers, e.g. for touch screens or touch pads, characterised by the transducing means by capacitive means
- G06F3/0445—Digitisers, e.g. for touch screens or touch pads, characterised by the transducing means by capacitive means using two or more layers of sensing electrodes, e.g. using two layers of electrodes separated by a dielectric layer
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- G—PHYSICS
- G06—COMPUTING; CALCULATING OR COUNTING
- G06F—ELECTRIC DIGITAL DATA PROCESSING
- G06F3/00—Input arrangements for transferring data to be processed into a form capable of being handled by the computer; Output arrangements for transferring data from processing unit to output unit, e.g. interface arrangements
- G06F3/01—Input arrangements or combined input and output arrangements for interaction between user and computer
- G06F3/03—Arrangements for converting the position or the displacement of a member into a coded form
- G06F3/041—Digitisers, e.g. for touch screens or touch pads, characterised by the transducing means
- G06F3/044—Digitisers, e.g. for touch screens or touch pads, characterised by the transducing means by capacitive means
- G06F3/0446—Digitisers, e.g. for touch screens or touch pads, characterised by the transducing means by capacitive means using a grid-like structure of electrodes in at least two directions, e.g. using row and column electrodes
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- G—PHYSICS
- G06—COMPUTING; CALCULATING OR COUNTING
- G06F—ELECTRIC DIGITAL DATA PROCESSING
- G06F3/00—Input arrangements for transferring data to be processed into a form capable of being handled by the computer; Output arrangements for transferring data from processing unit to output unit, e.g. interface arrangements
- G06F3/01—Input arrangements or combined input and output arrangements for interaction between user and computer
- G06F3/048—Interaction techniques based on graphical user interfaces [GUI]
- G06F3/0487—Interaction techniques based on graphical user interfaces [GUI] using specific features provided by the input device, e.g. functions controlled by the rotation of a mouse with dual sensing arrangements, or of the nature of the input device, e.g. tap gestures based on pressure sensed by a digitiser
- G06F3/0488—Interaction techniques based on graphical user interfaces [GUI] using specific features provided by the input device, e.g. functions controlled by the rotation of a mouse with dual sensing arrangements, or of the nature of the input device, e.g. tap gestures based on pressure sensed by a digitiser using a touch-screen or digitiser, e.g. input of commands through traced gestures
- G06F3/04883—Interaction techniques based on graphical user interfaces [GUI] using specific features provided by the input device, e.g. functions controlled by the rotation of a mouse with dual sensing arrangements, or of the nature of the input device, e.g. tap gestures based on pressure sensed by a digitiser using a touch-screen or digitiser, e.g. input of commands through traced gestures for inputting data by handwriting, e.g. gesture or text
-
- G—PHYSICS
- G06—COMPUTING; CALCULATING OR COUNTING
- G06F—ELECTRIC DIGITAL DATA PROCESSING
- G06F3/00—Input arrangements for transferring data to be processed into a form capable of being handled by the computer; Output arrangements for transferring data from processing unit to output unit, e.g. interface arrangements
- G06F3/01—Input arrangements or combined input and output arrangements for interaction between user and computer
- G06F3/048—Interaction techniques based on graphical user interfaces [GUI]
- G06F3/0487—Interaction techniques based on graphical user interfaces [GUI] using specific features provided by the input device, e.g. functions controlled by the rotation of a mouse with dual sensing arrangements, or of the nature of the input device, e.g. tap gestures based on pressure sensed by a digitiser
- G06F3/0489—Interaction techniques based on graphical user interfaces [GUI] using specific features provided by the input device, e.g. functions controlled by the rotation of a mouse with dual sensing arrangements, or of the nature of the input device, e.g. tap gestures based on pressure sensed by a digitiser using dedicated keyboard keys or combinations thereof
- G06F3/04892—Arrangements for controlling cursor position based on codes indicative of cursor displacements from one discrete location to another, e.g. using cursor control keys associated to different directions or using the tab key
Definitions
- the present invention relates to object position and pressure sensing transducers and systems. More particularly, the present invention relates to object position and pressure recognition useful in applications such as cursor movement for computing devices and other applications, and especially for enhancing the scrollbar feature in applications for computing devices.
- the interface between the computer system user and the computer system is a graphical interface on a visual display.
- the operating system presents in the graphical interface a "window" through which applications such as word processing, spreadsheets, database, etc. are viewed. It is common in applications to create electronic documents which are also depicted graphically in the visual display.
- applications have a variety of features and controls. One common way of accessing these features and controls is by moving a graphical cursor over the graphical display of the feature by some manner of object position detector. The feature is then often activated by the object position detector itself.
- Resistive-membrane position sensors are known and used in several applications. However, they generally suffer from poor resolution, the sensor surface is exposed to the user and is thus subject to wear. In addition, resistive-membrane touch sensors are relatively expensive.
- a one-surface approach requires a user to be grounded to the sensor for reliable operation. This cannot be guaranteed in portable computers.
- An example of a one- surface approach is the UnMouse product by MicroTouch, of Wilmington, MA A two-surface approach has poorer resolution and potentially will wear out very quickly in time.
- Resistive tablets are taught by United States Patent No. 4,680,430 to Yoshikawa, United States Patent No. 3,497,617 to Ellis and many others.
- the drawback of all such approaches is the high power consumption and the high cost of the resistive membrane employed.
- SAW Surface Acoustic Wave
- Strain gauge or pressure plate approaches are an interesting position sensing technology, but suffer from several drawbacks.
- This approach may employ piezo-electric transducers.
- One drawback is that the piezo phenomena is an AC phenomena and may be sensitive to the user's rate of movement.
- strain gauge or pressure plate approaches are somewhat expensive because special sensors are required.
- Optical approaches are also possible but are somewhat limited for several reasons. All would require light generation which will require external components and increase cost and power drain. For example, a "finger-breaking" infra-red matrix position detector consumes high power and suffers from relatively poor resolution.
- Desirable attributes of such a device are low power, low profile, high resolution, low cost, fast response, and ability to operate reliably when the finger carries electrical noise, or when the touch surface is contaminated with dirt or moisture.
- United States Patent No. 4,550,221 to Mabusth teaches a capacitive tablet wherein the effective capacitance to "virtual ground" is measured by an oscillating signal. Each row or column is polled sequentially, and a rudimentary form of inte ⁇ olation is applied to resolve the position between two rows or columns. An attempt is made to address the problem of electrical interference by averaging over many cycles of the oscillating waveform. The problem of contamination is addressed by sensing when no finger was present, and applying a periodic calibration during such no-finger-present periods.
- United States Patent No. 4,639,720 to Rympalski teaches a tablet for sensing the position of a stylus.
- the stylus alters the transcapacitance coupling between row and column electrodes, which are scanned sequentially.
- United States Patent No. 4,736,191 to Matzke teaches a radial electrode arrangement under the space bar of a keyboard, to be activated by touching with a thumb. This patent teaches the use of total touch capacitance, as an indication of the touch pressure, to control the velocity of cursor motion. Pulsed sequential polling is employed to address the effects of electrical interference.
- Gruaz uses a drive and sense signal set (2 signals) in the touch matrix and like Evans relies on the attenuation effect of a finger to modulate the drive signal.
- the touch matrix is sequentially scanned to read the response of each matrix line.
- An interpolation program selects the two largest adjacent signals in both dimensions to determine the finger location, and ratiometrically determines the effective position from those 4 numbers.
- Gerpheide, PCT apphcation US90/04584, pubUcation No. W091/03039, United States Patent No. 5,305,017 applies to a touch pad system a variation of the virtual dipole approach of Greanias.
- Gerpheide teaches the application of an oscillating potential of a given frequency and phase to all electrodes on one side of the virtual dipole,and an oscillating potential of the same frequency and opposite phase to those on the other side.
- Electronic circuits develop a "balance signal" which is zero when no finger is present, and which has one polarity if a finger is on one side of the center of the virtual dipole, and the opposite polarity if the finger is on the opposite side.
- the virtual dipole is scanned sequentially across the tablet. Once the finger is located, it is "tracked” by moving the virtual dipole toward the finger once the finger has moved more than one row or column.
- the virtual dipole method operates by generating a balance signal that is zero when the capacitance does not vary with distance, it only senses the perimeter of the finger contact area, rather than the entire contact area. Because the method relies on synchronous detection of the exciting signal, it must average for long periods to reject electrical interference, and hence it is slow. The averaging time required by this method, together with the necessity to search sequentially for a new finger contact once a previous contact is lost, makes this method, like those before it, fall short of the requirements for a fast pointing device that is not affected by electrical interference.
- scroUing feature One of the most common controls in appUcations is a scroUing feature.
- Those of ordinary skill in the art are readily familiar with the scroUing feature of documents in graphical displays. With this feature, a user can move through a document line by Une. Unfortunately, the scrolUng takes place at a constant rate.
- This feature is often accessed with an object position detector which is used to move the cursor over the scroll arrow. The document is then scrolled a constant rate by activating the scroU arrow, often with the object position detector. If the object position detector is a "mouse", the scroll arrow can be activated by depressing and holding the mouse button.
- Yet another object of the present invention is to provide a two-dimensional capacitive sensing system equipped with a separate set of drive/sense electronics for each row and for each column of a capacitive tablet, wherein all row electrodes are sensed simultaneously, and all column electrodes are sensed simultaneously and wherein the information defining the location of a finger or other conductive object is processed in digital form.
- the present invention comprises a position-sensing technology particularly useful for applications where finger position information is needed, such as in computer "mouse" or trackbaU environments.
- the position-sensing technology of the present invention has much more general application than a computer mouse, because its sensor can detect and report if one or more points are being touched.
- the detector can sense the pressure of the touch.
- a position sensing system includes a position sensing transducer comprising a touch-sensitive surface disposed on a substrate, such as a printed circuit board, including a matrix of conductive Unes.
- a first set of conductive Unes runs in a first direction and is insulated from a second set of conductive lines running in a second direction generaUy perpendicular to the first direction.
- An insulating layer is disposed over the first and second sets of conductive Unes. The insulating layer is thin enough to promote significant capacitive coupUng between a finger placed on its surface and the first and second sets of conductive Unes.
- Sensing electronics respond to the proximity of a finger, conductive object, or an object of high dielectric constant (i.e., greater than about 5) to translate the capacitance changes of the conductors caused by object proximity into digital information which is processed to derive position and touch pressure information. Its output is a simple X, Y and pressure value, Z, of the one object on its surface.
- fingers are to be considered interchangeable with conductive objects and objects of high dielectric constant.
- ParaUel drive sense techniques allow input samples to be taken simultaneously, thus aU channels are affected by the same phase of an interfering electrical signal, greatly simpUfying the signal processing and noise filtering.
- the voltages on aU of the X lines of the sensor matrix are simultaneously moved, while the voltages of the Y Unes are held at a constant voltage, with the complete set of sampled points simultaneously giving a profile of the finger in the X dimension.
- the voltages on all of the Y lines of the sensor matrix are simultaneously moved, while the voltages of the X lines are held at a constant voltage to obtain a complete set of sampled points simultaneously giving a profile of the finger in the other dimension.
- the voltages on all of the X lines of the sensor matrix are simultaneously moved in a positive direction, while the voltages of the Y lines are moved in a negative direction.
- the voltages on aU of the X Unes of the sensor matrix are simultaneously moved in a negative direction, while the voltages of the Y lines are moved in a positive direction.
- both embodiments then take these profiles and derive a digital value representing the centroid for X and Y position and derive a second digital value for the Z pressure information.
- the digital information may be directly used by a host computer. Analog processing of the capacitive information may also be used according to the present invention.
- a scroll feature modifier uses the Z pressure information to make the rate of scroUing a function of the pressure information.
- the position sensor of these embodiments can only report the position of one object on its sensor surface. If more than one object is present, the position sensor of this embodiment computes the centroid position of the combined set of objects. However, unlike prior art, because the entire pad is being profiled, enough information is available to discern simple multi-finger gestures to aUow for a more powerful user interface.
- noise reduction techniques are integrated into the system.
- a capacitance measurement technique which is easier to caUbrate and implement is employed.
- FIG. 1 is an overall block diagram of the capacitive position sensing system of the present invention.
- FIG. 2a is a top view of an object position sensor transducer according to a presently preferred embodiment of the invention showing the object position sensor surface layer including a top conductive trace layer and conductive pads connected to a bottom trace layer.
- FIG. 2b is a bottom view of the object position sensor transducer of FIG. 2a showing the bottom conductive trace layer.
- FIG. 2c is a composite view of the object position sensor transducer of FIGS. 2a and 2b showing both the top and bottom conductive trace layers.
- FIG. 2d is a cross-sectional view of the object position sensor transducer of FIGS. 2a-2c.
- FIG. 3 is a block diagram of sensor decoding electronics which may be used with the sensor transducer in accordance with a preferred embodiment of the present invention.
- FIG. 4a is a simplified schematic diagram of a charge integrator circuit which may be used in the present invention.
- FIG. 4b is an iUustrative schematic diagram of the charge integrator circuit of FIG. 4a.
- FIG. 5 is a timing diagram of the operation of charge integrator circuit of FIGS. 4a and 4b.
- FIG. 6 is a schematic diagram of an iUustrative filter and sample/hold circuit for use in the present invention.
- FIG. 7 is a more detaUed block diagram of a presently preferred arrangement of A/D converters for use in the present invention.
- FIG. 8 is a block diagram of an Ulustrative arithmetic unit which may be used in the present invention.
- FIG. 9 is a block diagram of a cahbration unit which may be used with the arithmetic unit of FIG. 8.
- FIG. 10 is a schematic diagram of a bias voltage generating circuit useful in the present invention.
- FIG. 11 is a diagram of the sensing plane iUustrating the edge motion feature of the object position sensor of the present invention.
- FIG. 12 is a schematic diagram iUustrating hardware implementation of the determination of whether a finger or other object is present in the peripheral regions of the sensing plane.
- FIG. 13 is a schematic diagram iUustrating hardware implementation of the edge motion feature of the present invention.
- FIGS. 14a-14c are flow diagrams illustrating a process according to the present invention for recognizing tap and drag gestures.
- the present invention brings together in combination a number of unique features which allow for new applications not before possible. Because the object position sensor of the present invention has very low power requirements, it is beneficial for use in battery operated or low power applications such as lap top or portable computers . It is also a very low cost solution, has no moving parts (and is therefore virtuaUy maintenance free), and uses the existing printed circuit board traces for sensors.
- the sensing technology of the present invention can be integrated into a computer motherboard to even further lower its cost in computer applications. Similarly, in other applications the sensor can be part of an already existent circuit board. Because of its smaU size and low profile, the sensor technology of the present invention is useful in lap top or portable applications where volume is an important consideration.
- the sensor technology of the present invention requires circuit board space for only a single sensor interface chip that can interface directly to a microprocessor, plus the area needed on the printed circuit board for sensing.
- Capacitive position sensing system 6 can accurately determine the position of a finger 8 or other conductive object proximate to or touching a sensing plane 10.
- the capacitance of a plurahty of conductive lines running in a first direction e.g.,
- X is sensed by X input processing circuitry 12 and the capacitance of a plurahty of conductive lines running in a second direction (e.g., "Y") is sensed by Y input processing circuitry 14.
- the sensed capacitance values are digitized in both X input processing circuitry 12 and Y input processing circuitry 14.
- the outputs of X input processing circuitry 12 and Y input processing circuitry 14 are presented to arithmetic unit 16, which uses the digital information to derive digital information representing the position and pressure of the finger 8 or other conductive object relative to the sensing plane 10.
- the X, Y, and Z outputs of arithmetic unit 16 are directed to motion unit 18 which provides the cursor motion direction signals to the host computer.
- the X, Y, and Z outputs of arithmetic unit 16 are also directed to gesture unit 20, which is used to recognize certain finger gestures performed by a user on sensing plane 10.
- the virtual button output from gesture unit 20 may be used by motion unit 18 to implement some of the functionahty of motion unit 18.
- the sensor material can be anything that aUows creation of a conductive X/Y matrix of pads. This includes not only standard PC boards, but also includes but is not Umited to flexible PC boards, conductive elastomer materials, silk-screened conductive Unes, and piezo-electric Kynar plastic materials. This renders it useful as well in any portable equipment application or in human interface where the sensor needs to be molded to fit within the hand.
- the sensor can be conformed to any three dimensional surface. Copper can be plated in two layers on most any surface contour producing the sensor. This will allow the sensor to be adapted to the best ergonomic form needed for any particular application. This coupled with the "Ught-touch" feature wUl make it effortless to use in many applications.
- the sensor can also be used in an indirect manner, i.e it can have an insulating foam material covered by a conductive layer over the touch sensing surface and be used to detect any object (not just conductive) that presses against it's surface. Small sensor areas are practical, i.e., a presently conceived embodiment takes about 1.5"x 1.5" of area, however those of ordinary skill in the art will recognize that the area is scaleable for different applications.
- the matrix area is scaleable by either varying the matrix trace spacing or by varying the number of traces. Large sensor areas are practical where more information is needed.
- the sensor technology of the present invention also provides finger pressure information.
- This additional dimension of information may be used by programs to control special features such as "brush- width” modes in Paint programs, special menu accesses, etc., allowing provision of a more natural sensory input to computers. It has also been found useful for implementing "mouse click and drag” modes and for simple input gestures.
- the scroll rate is made a function of the Z pressure information.
- the rate of scrolling is dictated by the pressure information Z obtained from the arithmetic unit 16 through the touchpad 20. As the pressure information Z varies, so does the scroUing rate.
- the sense system of the present invention depends on a transducer device capable of providing position and pressure information regarding the object contacting the transducer.
- a transducer device capable of providing position and pressure information regarding the object contacting the transducer.
- FIGS. 2a-2d top, bottom, composite, and cross-sectional views, respectively, are shown of a presently-preferred sensing plane 10 comprising a touch sensor array 22 for use in the present invention. Since capacitance is exploited by this embodiment of the present invention, the surface of touch sensor array 22 is designed to maximize the capacitive coupling to a finger or other conductive object.
- a presently preferred touch sensor array 22 comprises a substrate 24 including a set of first conductive traces 26 disposed on a top surface 28 thereof and run in a first direction to comprise row positions of the array.
- a second set of conductive traces 30 are disposed on a bottom surface 32 thereof and run in a second direction preferably orthogonal to the first direction to form the column positions of the array.
- the top and bottom conductive traces 26 and 30 are alternately in contact with periodic sense pads 34 comprising enlarged areas, shown as diamonds in FIGS. 2a-2c. While sense pads 34 are shown as diamonds in RGS. 2a- 2c, any shape, such as circles, which allows them to be closely packed is equivalent for pu ⁇ oses of this invention.
- first conductive traces 26 wiU be referred to as being oriented in the "X” or “row” direction and may be referred to herein sometimes as "X lines” and the second conductive traces 30 wUl be referred to as being oriented in the "Y” or “column” direction and may be referred to herein sometimes as "Y lines”.
- sense pads 34 The number and spacing of these sense pads 34 depends upon the resolution desired. For example, in an actual embodiment constructed according to the principles of the present invention, a 0.10 inch center-to-center diamond-shaped pattern of conductive pads disposed along a matrix of 15 rows and 15 columns of conductors is employed. Every other sense pad 34 in each direction in die pad pattern is connected to conductive traces on the top and bottom surfaces 28 and 32, respectively of substrate 24.
- Substrate 24 may be a printed circuit board, a flexible circuit board or any of a number of avaUable circuit interconnect technology structures. Its thickness is unimportant as long as contact may be made therethrough from the bottom conductive traces 30 to their sense pads 34 on the top surface 28.
- the printed circuit board comprising substrate 24 can be constructed using standard industry techniques. Board thickness is not important. Connections from the conductive pads 34 to the bottom traces 30 may be made employing standard plated-through hole techniques well known in the printed circuit board art.
- the substrate material 24 may have a thickness on the order of 0.005 to 0.010 inches. Then the diamonds on the upper surface 28 and the plated through holes that connect to the lower surface traces 30, can be omitted, further reducing the cost of the system.
- Insulating layer 36 is disposed over the sense pads 34 on top surface 28 to insulate a human finger or other object therefrom.
- Insulating layer 36 is preferably a thin layer (i.e., approximately 5 mUs) to keep capacitive coupling large and may comprise a material, such as mylar, chosen for its protective and ergonomic characteristics.
- the term "significant capacitive couphng" as used herein shall mean capacitive coupUng having a magnitude greater than about 0.5 pF.
- the first capacitive effect is trans-capacitance, or coupling between sense pads 34
- die second capacitive effect is self-capacitance, or coupling to virtual ground.
- Sensing circuitry is coupled to the sensor a ⁇ ay 22 of the present invention and responds to changes in either or both of these capacitances. This is important because the relative sizes of the two capacitances change gready depending on the user environment.
- the abiUty of the present invention to detect changes in both self capacitance and trans-capacitance results in a very versatile system having a wide range of appUcations.
- a position sensor system including touch sensor array 22 and associated position detection circuitry wiU detect a finger position on a matrix of printed circuit board traces via the capacitive effect of finger proximity to the sensor array 22.
- the position sensor system wiU report the X, Y position of a finger placed near the sensor array 22 to much finer resolution than the spacing between the row and column traces 26 and 30.
- the position sensor according to this embodiment of the invention wttl also report a Z value proportional to the outUne of that finger and hence indicative of the pressure with which the finger contacts the surface of insulating layer 36 over the sensing array 22.
- a very sensitive, light-touch detector circuit may be provided using adaptive analog and digital VLSI techniques.
- the circuit of the present invention is very robust and calibrates out process and systematic errors.
- the detector circuit of the present invention wiU process the capacitive input information and provide digital information which may be presented directly to a microprocessor.
- sensing circuitry is contained on a single sensor processor integrated circuit chip.
- the sensor processor chip can have any number of X and Y "matrix" inputs. The number of X and Y inputs does not have to be equal.
- the Integrated circuit has a digital bus as output.
- the sensor array has 15 traces in both the X and Y directions.
- the sensor processor chip thus has 15 X inputs and 15 Y inputs.
- An actual embodiment constructed according to the principles of the present invention employed 18 traces in the X direction and 24 traces in the Y direction.
- Those of ordinary skiU in the art wUl recognize that the size of the sensing matrix which may be employed in the present invention is arbitrary and wiU be dictated largely by design choice.
- the X and Y matrix nodes are driven and sensed in paraUel, with the capacitive information from each Une indicating how close a finger is to that node.
- the scanned information provides a profile of the finger proximity in each dimension.
- die profile centroid is derived in both the X and Y directions and is the position in that dimension.
- the profile curve of proximity is also integrated to provide the Z information.
- a second drive/sense method the voltages on all of the X lines of the sensor matrix are simultaneously moved in a positive direction, whUe the voltages of the Y lines are moved in a negative direction.
- die voltages on aU of the X Unes of the sensor matrix are simultaneously moved in a negative direction, while the voltages of the Y lines are moved in a positive direction.
- This second drive/sense mediod accentuates transcapacitance and de- emphasizes virtual ground capacitance.
- those of ordinary skiU in the art wUl recognize that order of these two steps is somewhat arbitrary and may be reversed.
- FIG. 3 a block diagram of the presentiy preferred sensing circuitry 40 for use according to the present invention is presented.
- This block diagram, and the accompanying disclosure relates to the sensing circuitry in one dimension (X) only, and includes the X input processing circuitry 12 of FIG. 1.
- X the sensing circuitry
- Y the opposite
- Such skUled persons wdl further note that the two dimensions do not need to be orthogonal to one another. For example, they can be radial or of any other nature to match the contour of the touch sensor array and other needs of the system.
- the technology disclosed herein could be apphed as well to a one-dimensional case where only one set of conductive traces is used.
- the capacitance at each sensor matrix node is represented by equivalent capacitors 42-1 through 42-n.
- the capacitance of capacitors 42-1 through 42-n comprises the capacitance of the matrix conductors and has a characteristic background value when no object (e.g., a finger) is proximate to the sensing plane of the sensor matrix. As an object approaches the sensing plane the capacitance of capacitors 42- 1 through 42-n increases in proportion to the size and proximity of the object.
- the capacitance at each sensor matrix node is measured simultaneously using charge integrator circuits 44-1 through 44-n.
- Charge-integrator circuits 44- 1 through 44-n serve to inject charge into the capacitances 42-1 through 42-n, respectively, and to develop an output voltage proportional to the capacitance sensed on the corresponding X matrix line.
- charge-integrator circuits 44-1 through 44-n are shown as bidirectional ampUfier symbols.
- Each charge-integrator circuit 44- 1 through 44-n is supplied with an operating bias voltage by bias-voltage generating circuit 46.
- the phrase "proportional to the capacitance" means mat the voltage signal generated is a monotonic function of die sensed capacitance.
- die voltage is directly and linearly proportional to die capacitance sensed.
- monotonic functions including but not Umited to inverse proportionaUty, and non-linear proportionaUty such as logarithmic or exponential functions, could be employed in the present invention without departing from the principles disclosed herein.
- current-sensing as weU as voltage-sensing techniques could be employed.
- the capacitance measurements are performed simultaneously across all inputs in one dimension to overcome a problem which is inherent in all prior art approaches that scan individual inputs.
- the problem with the prior-art approach is that it is sensitive to high frequency and large ampUtude noise (large dv/dt noise) that is coupled to die circuit via the touching object.
- large ampUtude noise large dv/dt noise
- Such noise may distort the finger profile because of noise appearing in a later scan cycle but not an earUer one, due to a change in the noise level.
- the present invention overcomes this problem by "taking a snapshot" of aU inputs simultaneously in X and then Y directions (or visa versa). Because the injected noise is proportional to the finger signal strengtii across all inputs, it is therefore symmetric around the finger centroid. Because it is symmetric around die finger centroid it does not affect the finger position. Additionally, die charge ampUfier performs a differential measuring function to further reject common-mode noise.
- filter circuits 48-1 through 48-n are implemented as sample and hold switched capacitor filters.
- the desired voltage is captured by die filter circuits 48-1 rough 48-n.
- the filter circuits 48-1 through 48-n wdl filter out any high frequency noise from the sensed signal. This is accomplished by choosing the capacitor for die filter to be much larger man the output capacitance of charge integrator circuits 44- 1 through 44-n.
- those of ordinary skill in the art wdl recognize diat die switched capacitor filter circuits 48-1 through 48-n will capture the desired voltages and store them.
- the capacitance information obtained in voltage form from the capacitance measurements is digitized and processed in digital format. Accordingly, me voltages stored by filter circuits 48-1 through 48-n are stored in sample/hold circuits 50-1 through 50-n so that the remainder of the circuitry processes input data taken at the same time. Sample/hold circuits 50-1 through 50-n may be configured as conventional sample/hold circuits as is well known in the art.
- A/D converters 52 resolve the input voltage to a 10-bit wide digital signal (a resolution of one part in 1,024), although those of ordinary skill in the art wdl reaUze that other resolutions may be employed.
- A/D converters 52 may be conventional successive approximation type converters as is known in the art.
- the background level (no object present) of the charge integrator outputs wUl be about 1 volt.
- the ⁇ V resulting from the presence of a finger or other object wiU typicaUy be about 0.4 volt.
- the voltage range of the A D converters 52 should therefore be in the range of between about 1-2 volts.
- V-- ⁇ and V max minimum and maximum voltage reference points for the A/D converters. It has been found that noise wdl cause position jitter if these reference voltages are fixed points.
- a solution to this problem which is employed in the present invention is to dynamically generate the V- j ⁇ , and V,,- ⁇ reference voltages from reference capacitances 42-Vmin and 42- Vmax, sensed by charge integrator circuits 44-Vmin and 44- Vmax and processed by filter circuits 48-Vmin and 48-Vmax and stored in sample/hold circuits 50- Vmin and 50- Vmax .
- any common mode noise present when the signals are sampled from the sensor array wUl also be present in the V-- ⁇ and V ma ⁇ reference voltage values and wiU tend to cancel.
- reference capacitances 44-Vmin and 44- Vmax may either be discrete capacitors or extra traces in the sensor a ⁇ ay.
- the V, ⁇ reference voltage is generated from a capacitor having a value equal to the lowest capacitance expected to be encountered in the sensor array with no object present (about 12pF assuming a 2 inch square sensor array).
- the V max reference voltage is generated from a capacitor having a value equal to die largest capacitance expected to be encountered in die sensor array with an object present (about 16pF assuming a 2 inch square sensor array).
- arithmetic unit 16 The outputs of A/D converters 52 provide inputs to arithmetic unit 16.
- the function of arithmetic unit 16 is to compute die weighted average of the signals on die individual sense lines in both the X and Y directions in the touch sensor array 22.
- arithmetic unit 16 is shared by the X input processing circuitry 12 and the Y input processing circuitry 14 as shown in FIG. 1.
- Control circuitry 56 of FIG. 3 orchestrates the operation of the remainder of die circuitry.
- control circuitry 56 is present to manage the signal flow.
- the functions performed by control circuitry 56 may be conventionaUy developed via what is commonly known in the art as a state machine or microcontroller.
- Charge integrator circuit 44 is shown as a simpUfied schematic diagram in FIG. 4a and as an iUustrative schematic diagram in FIG. 4b.
- the timing of the operation of charge integrator circuit 44 is shown in FIG. 5. These timing signals are provided by die controller block 56.
- Charge integrator circuit 44 is based on die fundamental physical phenomena of using a current to charge a capacitor. If the capacitor is charged for a constant time by a constant current, then a voltage wUl be produced on the capacitor which is inversely proportional to die capacitance.
- the capacitance to be charged is the sensor matrix line capacitance 42 in parallel with an internal capacitor. This internal capacitor wiU contain d e voltage of interest
- a charge integrator circuit input node 60 is connected to one of the X (or Y) Unes of die sensor matrix.
- a first shorting switch 62 is connected between the charge integrator circuit input node 60 and V DD , the positive supply rail.
- a second shorting switch 64 is connected between the charge integrator circuit input node 60 and ground, die negative supply rail.
- a positive constant current source 66 is connected to V DD , the positive supply rail and to d e charge integrator circuit input node 60 and through a first current source switch 68.
- a negative constant current source 70 is connected to ground and to the charge integrator circuit input node 60 and dirough a second current source switch 72. It is obvious that other high and low voltage rails could be used in place of V DD and ground.
- a first internal capacitor 74 is connected between V DD and output node 76 of charge integrator circuit 44.
- a positive voltage storage switch 78 is connected between output node 76 and input node 60.
- a second internal capacitor 80 has one of its plates connected to ground through a switch 82 and to output node 76 of charge integrator circuit 44 through a switch 84, and the other one of its plates connected to input node 60 through a negative voltage storage switch 86 and to V DD through a switch 88.
- the capacitance of first and second internal capacitances 74 and 80 should be a small fraction (i.e., about 10%) of the capacitance of the individual sensor matrix Unes.
- d e sensor matrix line capacitance wUl be about lOpF and die capacitance of capacitors 74 and 80 should be about lpF.
- the approach used is a differential measurement for added noise immunity, the benefit of which is that any low frequency common mode noise gets subtracted out.
- the sensor matrix line is momentarily shorted to V D n through switch 62, switch 78 is closed connecting capacitor 74 in parallel with die capacitance of me sensor line. Then the parallel capacitor combination is discharged with a constant current from current source 70 through switch 72 for a fixed time period. At the end of the fixed time period, switch 78 is opened, dius storing the voltage on the sensor matrix line on capacitor 74.
- the sensor line is then momentarily shorted to ground dirough switch 64, and switches 82 and 86 are closed to place capacitor 80 in paraUel witii die capacitance of the sensor line.
- Switch 68 is closed and die parallel capacitor combination is charged with a constant current from current source 66 for a fixed time period equal to the fixed time period of die first cycle.
- switch 86 is opened, tiius storing the voltage on the sensor matrix line on capacitor 80.
- the first and second measured voltages are then averaged. This is accomplished by opening switch 82 and closing switches 88 and 84, which places capacitor 80 in parallel widi capacitor 74. Because capacitors 74 and 80 have die same capacitance, the resulting voltage across them is equal to the average of the voltages across each individuaUy. This final result is the value that is then passed on to die appropriate one of filter circuits 48-1 through 48-n.
- the low frequency noise notably 50/60 Hz and tiieir harmonics, behaves as a DC current component that adds in one measurement and subtracts in the other. When the two results are added together that noise component averages to zero.
- the amount of noise rejection is a function of how quickly in succession the two opposing charge-up and charge-down cycles are performed as wiU be disclosed herein. One of the reasons for the choice of this charge integrator circuit is that it allows measurements to be taken quickly.
- FIG. 4b a more complete schematic diagram of an iUustrative embodiment of charge integrator circuit 44 of the simplified diagram of FIG. 4a is shown.
- Input node 60 is shown connected to V DD and ground through pass gates 90 and 92, which replace switches 62 and 64 of FIG. 4a.
- Pass gate 90 is controlled by a signal ResetUp presented to its control input and pass gate 92 is controlled by a signal ResetDn presented to its control input.
- pass gates 90 and 92, as weU as aU of the otiier pass gates which are represented by the same symbol in FIG. 4b may be conventional CMOS pass gates as are known in the art.
- the convention used herein is that the pass gate wiU be off when its control input is held low and wiU be on and present a low impedance connection when its control input is held high.
- P-Channel MOS transistors 94 and 96 are configured as a current mirror.
- P-Channel MOS transistor 94 serves as the current source 66 and pass gate 98 serves as switch 68 of FIG. 4a.
- the control input of pass gate 98 is controlled by a signal StepUp.
- N-Channel MOS transistors 100 and 102 are also configured as a current mirror. N-Channel
- MOS transistor 100 serves as the current source 70 and pass gate 104 serves as switch 72 of FIG. 4a.
- the control input of pass gate 104 is controlled by a signal StepD ⁇ .
- P-Channel MOS transistor 106 and N-Channel MOS transistor 108 are placed in series with P-Channel MOS cu ⁇ ent mirror transistor 96 and N-Channel MOS current mirror transistor 102.
- the control gate of P-Channel MOS transistor 106 is driven by an enable signal EN, which turns on P-Channel MOS transistor 106 to energize the current mirrors.
- This device is used as a power conservation device so that the charge integrator circuit 44 may be turned off to conserve power when it is not in use.
- N-Channel MOS transistor 108 has its gate driven by a reference voltage Vbias, which sets the current through current mirror transistors 96 and 108.
- Vbias is set by a servo feedback circuit as wiU be disclosed in more detail witii reference to FIG. 10.
- wiU be disclosed in more detail witii reference to FIG. 10.
- this embodiment aUows caUbration to occur in real time (via long time constant feedback) thereby zeroing out any long term effects due to sensor environmental changes.
- Vbias is common for all charge integrator circuits 44- 1 through 44-n and 44- Vmax and 44- Vmin.
- MOS transistors 102 and 108 may provide temperature compensation. This is accompUshed by taking advantage of the fact that the tiireshold of N-Channel MOS transistor 108 reduces with temperature while the mobUity of both N-Channel MOS transistors 102 and 108 reduce witii temperature.
- the threshold reduction has the effect of increasing the current while the mobiUty reduction has the effect of decreasing die current. By proper device sizing these effects can cancel each other out over a significant part of the operating range.
- Capacitor 74 has one plate connected to V DD and the other plate connected to the output node 76 and to the input node 60 through pass gate 110, shown as switch 78 in FIG. 4a.
- the control input of pass gate 110 is driven by the control signal SUp.
- One plate of capacitor 80 is connected to input node 60 through pass gate 112 (switch 86 in FIG. 4a) and to VDD through pass gate 114 (switch 82 in FIG. 4a).
- the control input of pass gate 112 is driven by the control signal SDn and the control input of pass gate 114 is driven by die control signal ChUp.
- the other plate of capacitor 80 is connected to ground through N-Channel MOS transistor 116
- pass gate 118 is driven by control signal Share.
- First die EN (enable) control signal goes active by going to Ov. This turns on the current mirrors and energizes the charge and discharge current sources, MOS transistors 94 and 100.
- the ResetUp control signal is active high at this time, which shorts the input node 60 (and the sensor line to which it is connected) to V DD .
- the SUp control signal is also active high at this time which connects capacitor 74 and the output node 76 to input node 60. This arrangement guarantees that the following discharge portion of the operating cycle always starts from a known equ ⁇ ibrium state.
- StepDn The discharge process starts after ResetUp control signal goes inactive.
- the StepDn control signal goes active, connecting MOS transistor 100, the discharge current source, to the input node 60 and its associated sensor line.
- StepDn is active for a set amount of time, and die negative constant current source discharges the combined capacitance of the sensor line and capacitor 74 thus lowering its voltage during that time.
- StepDn is then turned off.
- a short time later the SUp control signal goes inactive, storing die measured voltage on capacitor 74. That ends the discharge cycle.
- the ResetDn control signal becomes active and shorts the sensor line to ground.
- the SDn and ChDn control signals become active and connect capacitor 80 between ground and die sensor line. Capacitor 80 is discharged to ground, guaranteeing that die following charge up cycle always starts from a known state.
- the charge up cycle starts after ResetDn control signal becomes inactive and the StepUp control signal becomes active.
- the current charging source MOS transistor 94
- MOS transistor 94 is connected to the sensor line and suppUes a constant current to charge the sensor line by increasing the voltage tiiereon.
- the StepUp control signal is active for a set amount of time (preferably equal to die time for the previously mentioned cycle) allowing the capacitance to charge, and then it is turned off.
- the SDn control signal then goes inactive, leaving the measured voltage across capacitor 80.
- the averaging cycle now starts. First the voltage on capacitor 80 is level shifted. This is done by the ChDn control signal going inactive, letting one plate of the capacitor 80 float. Then the ChUp control signal goes active, connecting the second plate of the capacitor to V DD . Then the
- Share control signal becomes active which connects the first plate of capacitor 80 to output node 76, thus placing capacitors 74 and 80 in parallel. This has the effect of averaging the voltages across the two capacitors, thus subtracting out common-mode noise as previously described. This average voltage is also then available on output node 76.
- the ChDn and ChUp signals should be asserted with respect to each other within a time period much less d an a quarter of the period of die noise to be cancelled in order to take advantage of mis feature of the present invention.
- FIG. 6 a schematic diagram of an iUustrative switched capacitor filter circuit 48 which may be used in die present invention is shown.
- this switched capacitor filter circuit which comprises an input node 120, a pass gate 122 having a control input driven by a Sample control signal, a capacitor 124 connected between the output of die pass gate 126 and a fixed voltage such as ground, and an output node comprising die common connection between d e capacitor 124 and the output of the pass gate 126.
- capacitor 116 wiU have a capacitance of about 10 pF.
- the switched capacitor filter 48 is in part a sample/hold circuit and has a filter time constant which is K times the period of sample, where K is the ratio of capacitor 124 to the sum of capacitors 74 and 80 of die charge integrator circuit 44 of FIGS. 4a and 4b to which it is connected.
- the switched capacitor filter circuit 48 further reduces noise injection in the system.
- RC filters may be employed in the present invention.
- A/D converters There are fewer A/D converters than there are lines in the touch sensor array, and die inputs to the A/D converters are multiplexed to share each of the individual A/D converters among several Unes in the touch sensor array.
- the arrangement in FIG. 7 is more efficient in the use of integrated circuit layout area than providing individual A/D converters for each input line.
- Analog multiplexer 130 has been conceptually drawn as six intemal multiplexer blocks 132-1 through 132-6.
- inputs taken from sample/hold circuits 50-1 through 50-4 are multiplexed to the output of intemal multiplexer block 132- 1 which drives A/D converter 52- 1.
- inputs taken from sample/hold circuits 50-5 through 50-8 are multiplexed to die output of intemal multiplexer block 132-2 which drives A/D converter 52-2; inputs taken from sample/hold circuits 50-9 through 50-12 are multiplexed to die output of intemal multiplexer block 132-3 which drives A/D converter 52-3; inputs taken from sample/hold circuits 50-13 dirough 50-16 are multiplexed to die output of intemal multiplexer block 132-4 which drives A/D converter 52-4; inputs taken from sample/hold circuits 50-17 through 50-20 are multiplexed to the output of intemal multiplexer block 132-5 which drives A/D converter 52-5; and inputs taken from sample/hold circuits 50-21 through 50-24 are multiplexed to the output of intemal multiplexer block 132-6 which drives A D converter 52-6.
- Analog multiplexer 130 has a set of control inputs schematically represented by bus 134.
- bus 134 schematically represented by Analog multiplexer 130.
- each of intemal multiplexers 132-1 through 132-6 are four-input multiplexers and tiius control bus 134 may comprise a two-bit bus for a one-of-four selection.
- tiius control bus 134 may comprise a two-bit bus for a one-of-four selection.
- multiplexers 132-1 through 132-6 wiU pass, in sequence, the analog voltages present on their first dirough fourth inputs on to the inputs of A/D converters 52-1 through 52-6 respectively. After the analog values have settled in the inputs of A/D converters 52-1 through 52-6, a CONVERT command is asserted on common A/D control Une 136 to begin the A/D conversion process.
- registers 138-1 through 138-6 may each comprise a two-word register, so tiiat one word may be read out of the registers to arithmetic unit 54 while a second word is being written into the registers in order to maximize the speed of the system.
- the design of such registers is conventional in d e art.
- aritiimetic unit 16 processes information from both the X and Y dimensions, i.e., from X input processing circuit 12 and Y input processing circuit 14 of FIG. 1.
- die object position in eitiier direction may be determined by evaluating the weighted average of the capacitances measured on die individual sense Une of the sensor array 10.
- the X direction is used, but those of ordinary skill in the art wiU recognize that the discussion applies to the determination of die weighted average in die Y direction as weU.
- die weighted average may be determined as foUows:
- arithmetic unit 16 includes X numerator and denominator accumulators 150 and 152 and Y numerator and denominator accumulators 154 and 156.
- the source of operand data for X numerator and denominator accumulators 150 and 152 and Y numerator and denominator accumulators 154 and 156 are the registers 138-1 through 138-6 in each (X and Y) direction of the sensor array 22 of FIG. 1.
- the X and Y denominator accumulators 152 and 156 sum up the digital results from the A/D conversions.
- the X and Y numerator accumulators 150 and 154 compute the weighted sum of die input data rather than die straight sum.
- Accumulators 150, 152, 154, and 156 may be configured as hardware elements or as software running on a microprocessor as will be readily understood by tiiose of ordinary skUl in the art.
- numerator accumulators 150 and 154 compute the expression of Eq. 4: n
- X and Y numerator and denominator offset registers 158, 160, 162, and 164 are subtracted from the results stored in die accumulators 150, 152, 154, and 156 in adders 166, 168, 170, and 172.
- Adder 166 subtracts the offset 0- ⁇ r ⁇ stored in X numerator offset register
- Adder 168 subtracts the offset O D ⁇ stored in X denominator offset register 160.
- Adder 170 subtracts the offset O NY stored in Y numerator offset register 162.
- Adder 172 subtracts the offset
- On ⁇ stored in Y denominator offset register 164 On ⁇ stored in Y denominator offset register 164.
- the numerator denominator pairs are divided by division blocks 174 and 176 to produce the X and Y position data, and the X and Y denominator pair is used by block 178 to produce Z axis (pressure) data.
- the function performed by block 178 wiU be disclosed later herein.
- the offsets O DX , O ⁇ , O DY , and O NY are sampled from the accumulator contents when directed by calibration unit 180.
- the architecture of the system of die present invention may be distributed in a number of ways, several of which involve the avadabiUty of a microprocessor, whether it be in a host computer to which die system of the present invention is connected or somewhere between the integrated circuit described herein and a host computer.
- Embodiments of e present invention are contemplated wherein the accumulated numerator and denominator values representing die summation terms are delivered to such a microprocessor along witii the O ⁇ and O D offset values for processing, or where all processing is accomplished by a programmed microprocessor as is known in the art.
- the numerator and denominator accumulators 150, 152, 154, and 156 are set to zero during system startup. If the multiplexed A/D converters as shown in FIG. 7 are employed, the digitized voltage data in the first word of register 138-1 (representing the voltage at the output of sample/hold circuit 50-1) is added to the sum in die accumulator and the result stored in the accumulator. In succession, die digitized voltage values stored in the first word of registers 138- 2 through 138-6 (representing the voltage at the outputs of sample/hold circuits 50-5, 50-9, 50- 17, and 50-21, respectively) are added to the sums in the accumulators and the results stored in the accumulators.
- A/D converters 52-1 through 52-6 may at this time be converting the voltages present at the outputs of sample hold circuits 50-2, 50-6, 50-10, 50- 14, 50-18, and 50-22 and storing the digitized values in the second words of registers 138-1 through 138-6 respectively.
- the digitized voltage values stored in the second words of registers 138-1 through 138-6 (representing the voltage at die outputs of-sample/hold circuits 50-2, 50-6, 50-10, 50-14, 50-18, and 50-22, respectively) are added to die sum in the accumulator and the result stored in die accumulator.
- the digitized voltage values stored in the first words of registers 138-1 through 138-6 (representing the voltage at the outputs of sample/hold circuits 50-3, 50-7, 50-11, 50- 15, 50-19, and 50-23, respectively) are added to the sum in the accumulator and the result stored in the accumulator, foUowed by digitized voltage values stored in die second words of registers 138-1 dirough 138-6 (representing the voltage at the outputs of sample/hold circuits 50- 4, 50-8, 50-12, 50-16, 50-20, and 50-24, respectively).
- the accumulators hold the sums of all of the individual digitized voltage values.
- the digital values stored in the O N and O D offset registers 158 and 164 are now respectively subtracted from die values stored in die numerator and denominator accumulators.
- the division operation in dividers 174 and 176 then completes the weighted average computation.
- the division operation may also be performed by an extemal microprocessor which can fetch the values stored in the accumulators or perform die accumulations itself.
- an extemal microprocessor which can fetch the values stored in the accumulators or perform die accumulations itself.
- the additional processing overhead presented to such extemal microprocessor by mis division operation is minimal.
- a dedicated microprocessor may be included on chip to handle these processing tasks without departing from the invention disclosed herein.
- the above disclosed processing takes place within about 1 milUsecond and may be repeatedly performed.
- Current mouse standards update position information 40 times per second, and tiius the apparatus of the present invention may easily be operated at tiiis repetition rate.
- the system of the present invention is adaptable to changing conditions, such as component aging, changing capacitance due to humidity, and contamination of the touch surface, etc.
- die present invention effectively minimizes ambient noise. According to die present invention, these effects are taken into consideration in three ways. First, the offset values O N and
- a servo-feedback circuit is provided to determine the bias voltage used to set the bias of the charge-integrator circuits 44-1 through 44-n.
- the reference voltage points for V max and V, ⁇ of the A/D converters are also dynamicaUy altered to increase the signal to noise margin.
- FIG. 9 a block diagram of a calibration unit 150 which may be used with die aritiimetic unit of FIG. 8 is presented.
- the calibration unit 150 executes an algorithm to establish the numerator and denominator offset values by attempting to determine when no finger or otiier conductive object is proximate to d e touch sensor array 22.
- die ON and O D offset values represent d e baseline values of die array capacitances with no object present. These values are also updated according to the present invention since baseline levels which are too low or too high have the effect of shifting die apparent position of the object depending on die sign of the error. These values are established by selection of the values read when no object is present at the sensor array 22. Since there is no extemal way to "know" when no object is present at sensor array 22, an algorithm according to anodier aspect of die present invention is used to establish and dynamicaUy update tiiese offset values. When the calibration unit sees a Z value which appears typical of the Z values when no finger is present, it instructs the offset registers (158, 160, 162, and 164 of FIG.
- the decision to update die offset values is based on the behavior of the sensor array 22 in only one of die X or Y directions, but when the decision is made all four offsets (O NX ,
- On X , ONY, and O ⁇ ) are updated.
- the decision to update may be individually made for each direction according to die criteria set forth herein.
- the cahbration algorithm works by monitoring changes in a selected one of the denominator accumulator values.
- die sensitivity to changes in capacitance of one of die sets of conductive lines in the touch sensor array 22 is greater than the sensitivity to changes in capacitance of the other one of the sets of conductive Unes in the touch sensor array 22.
- the set of conductive lines having the greater sensitivity to capacitance changes is the one which is physically located above die conductive Unes in the other direction and therefore closest to the touch surface of die sensor array 22.
- the upper set of conductive lines tends to partially shield the lower set of conductive Unes from capacitive changes occurring above the surface of the sensor array 22.
- the finger pressure is obtained by summing the capacitances measured on the sense Unes. This value is already present in the denominator accumulator after subtracting die offset O D . A finger is present if the pressure exceeds a suitable threshold value. This threshold may be chosen experiment-ally and is a function of surface material and circuit timing. The threshold may be adjusted to suit the tastes of the individual user.
- the pressure reported by the device is a simple function f(X D Y D ) of the denominators for die X and Y directions as implemented in block 178 of FIG. 8.
- Possible functions include choosing one preferred denominator value, or summing the denominators. In a presendy preferred embodiment, the smaller of the two denominators is chosen. This choice has the desirable effect of causing the pressure to go below die tiireshold if the finger moves sUghtly off the edge of the pad, where die X sensors are producing valid data, but the Y sensors are not, or vise versa. This acts as an electronic bezel which can take the place of a mechanical bezel at the periphery of the sensor area.
- the Y denominator is chosen for momtoring because it is the most sensitive.
- the chosen denominator is referred to as Z for the pu ⁇ oses of the calibration algorithm.
- the current saved offset value for this denominator is referred to as O_7.
- the goal of the calibration algorithm is to track gradual variations in the resting Z level whUe making sure not to calibrate to the finger, nor to calibrate to instantaneous spikes arising from noise.
- the calibration algorithm could be implemented in digital or analog hardware, or in software. In a current embodiment actually tested by the inventors, it is implemented in software.
- History buffer 184 which operates in conjunction with filter 182, keeps a "mnning average" of recent Z values.
- a is a constant factor between 0 and 1 and typically close to 1 and Z is the cu ⁇ ent Z value.
- alpha is approximately 0.95.
- the intention is for F z to change slowly enough to follow gradual variations, witiiout being greatly affected by short perturbations in Z.
- the filter 182 receives a signal ENABLE from control unit 186.
- the mnning average F z is updated based on new Z values only when ENABLE is asserted. If ENABLE is deasserted, F z remains constant and is unaffected by cu ⁇ ent Z.
- the history buffer 184 records the several most recent values of F z .
- die history buffer records the two previous F z values.
- the history buffer might be implemented as a shift register, circular queue, or analog delay Une.
- the history buffer receives a REWIND signal from control unit 186, it restores the cu ⁇ ent mnning average F z to the oldest saved value. It is as if the filter 182 were "retroactively" disabled for an amount of time corresponding to the depth of the history buffer.
- the pu ⁇ ose of the history buffer is to permit such retroactive disabUng.
- the current mnning average F z is compared against the cu ⁇ ent Z value and die cu ⁇ ent offset O z by absolute difference units 188 and 190, and comparator 192.
- Absolute difference unit 188 subtracts the values Z and F z and outputs the absolute value of their difference.
- Absolute difference unit 190 subtracts the values O z and F z and outputs the absolute value of tiieir difference.
- Comparator 192 asserts the UPDATE signal if the output of absolute difference unit
- the UPDATE signal wdl tend to be asserted when the mean value of Z shifts to a new resting level. It wiU tend not to be asserted when Z makes a brief excursion away from its normal resting level.
- the filter constant a determines die length of an excursion which wdl be considered "brief for this pu ⁇ ose.
- Subtractor unit 194 is a simple subtractor that computes the signed difference between Z and O z .
- This subtractor is actuaUy redundant with subtractor 172 in figure 8, and so may be merged with it in the actual implementation.
- the output C z of this subtractor is the cahbrated Z value, an estimate of the finger pressure. This pressure value is compared against a positive and negative Z direshold by comparators 196 and 198. These thresholds are shown as Z ⁇ and -Z ⁇ H , although tiiey are not actuaUy required to be equal in magnitude.
- pressure signal C z is greater than ⁇ H, the signal FINGER is asserted indicating the possible presence of a finger.
- the Z ⁇ - j threshold used by the cahbration unit is simdar to that used by the rest of the system to detect the presence of die finger, or it may have a different value. In the present embodiment, die calibration is set somewhat lower than the main J ⁇ to ensure diat die cahbration unit makes a conservative choice about the presence of a finger. If pressure signal C z is less than - ⁇ -j, the signal FORCE is asserted.
- O z is meant to be equal to die resting value of Z wim no finger present, and a finger can only increase the sensor capacitance and tiius the value of Z, a largely negative C z implies at die device must have inco ⁇ ectly cahbrated itself to a finger, which has just been removed.
- Calibration logic 200 uses tiiis fact to force a recaUbration now that the finger is no longer present.
- Control logic 186 is responsible for preventing mnning average F z from being influenced by Z values diat occur when a finger is present.
- Output ENABLE is generally off when the FINGER signal is tme, and on when the FINGER signal is false.
- the control logic when FINGER transitions from false to true, the control logic also pulses the REWIND signal. When FINGER transitions from tme to false, the control logic waits a short amount of time (comparable to the depdi of die history buffer) before asserting ENABLE. Thus, the running average is prevented from following Z whenever a finger is present, as well as for a short time before and after the finger is present.
- Calibration logic 200 produces signal RECAL from the outputs of the three comparators 192, 196, and 198.
- RECAL is asserted, the offset registers O N and O D wiU be reloaded from e cu ⁇ ent accumulator values.
- RECAL is produced from the foUowing logic equation:
- caUbration logic 200 a ⁇ anges to assert RECAL once when the system is first initiaUzed, possibly after a brief period to wait for the charge integrators and other circuits to stabdize.
- control logic 186 and calibration logic 200 From the descriptions of control logic 186 and calibration logic 200, it wiU be apparent to those of ordinary skdl in the art that these blocks can be readily configured using conventional logic as a matter of simple and routine logic design.
- caUbration algorithm described is not specific to the particular system of charge integrators and accumulators of the current invention. Rather, it could be employed in any touch sensor which produces proximity or pressure data in which it is desired to maintain a cahbration point reflecting the state of the sensor when no finger or spurious noise is present.
- bias voltage generating circuit 46 useful in the present invention is shown in schematic diagram form.
- all of the bias transistors 108 (FIG. 4b) of charge integrator circuits 44- 1 through 44-n have their gates connected to a single source of bias voltage, although persons of ordinary skiU in die art recognize that other anangements are possible.
- the bias voltage generating circuit 46 is an overdamped servo system.
- a reference source which approximates the cu ⁇ ent source function of a typical one of die charge integrator circuits 44-1 through 44-n includes a capacitor 202 having one of its plates grounded. The other one of its plates is connected to the V D D power supply through a first pass gate 204 and to a current source transistor 206 through a second passgate 208.
- a filter circuit 210 identical to the filter circuits 48-1 through 48-n and controlled by die same signal as filter circuits 48-1 through 48-n is connected to sample the voltage on capacitor 202 in the same manner that the filter-and-sample/hold circuits 48-1 through 48-n sample the voltages on the sensor conductor capacitances in the sensor array 22.
- the output of filter circuit 210 is fed to the non-inverting input of a weak transconductance ampHfier 212, having a bias cu ⁇ ent in the range of from about 0.1-0.2 ⁇ A.
- the inverting input of the transconductance amplifier 212 is connected to a fixed voltage of about 1 volt generated, for example, by diode 214 and resistor 216.
- the output of transconductance amplifier 212 is shunted by capacitor 218 and also by capacitor 220 through passgate 222.
- Capacitor 220 is chosen to be much larger than capacitor 218. In a typical embodiment of the present invention, capacitor 218 may be about 0.2pF and capacitor 220 may be about lOpF.
- Capacitor 220 is connected to the gate of N-Channel MOS transistor 224, which has its drain connected to the drain and gate of P-Channel MOS transistor 226 and its source connected to the drain and gate of N-Channel MOS transistor 228.
- the source of P-Channel MOS transistor 226 is connected to V D D and the source of N-Channel MOS transistor 228 is connected to ground.
- the common drain connection of transistors 224 and 228 is the bias voltage output node.
- An optional passgate 230 may be connected between a fixed voltage source (e.g., about 2 volts) and capacitor 220. Passgate 230 may be used to initialize die bias generating circuit 46 on startup by charging capacitor 220 to the fixed voltage.
- a fixed voltage source e.g., about 2 volts
- the filter circuit 210 takes a new sample. If the new sample differs from the previous sample, the output voltage of transconductance ampUfier 212 wdl change and start to charge or discharge capacitor 218 to a new voltage. Passgate 222 is switched on for a short time (i.e., about l ⁇ sec) and the voltages on capacitors 218 and 220 try to average themselves. Due to the large size difference between capacitors 218 and 220, capacitor 218 cannot supply enough charge to equalize the voltage during the period when passgate 222 is open. This anangement prevents large changes in bias voltage from cycle to cycle.
- Capacitor 202 should look as much as possible pie one of the sensor a ⁇ ay channels and has a value equal to the background capacitance of a typical sensor line, (i.e., with no object proximate or present capacitance component).
- Capacitor 202 may be formed in several ways. Capacitor 202 may comprise an extra sensor line in a part of the sensor a ⁇ ay, configured to approximate one of the active sensor Unes but shielded from finger capacitance by a ground plane, etc. Alternately, capacitor 202 may be a capacitor formed in the integrated circuit or connected thereto and having a value selected to match that of a typical sensor Une. In this respect, the signal source comprising capacitor 202 and filter circuit 210 is somewhat Uke the circuitry for generating the V--.- J - and V, ⁇ reference voltages, in that it mimics a typical sensor line.
- one of the actual sensor lines may be employed to set the bias voltage.
- the measured voltage on the two end-point sensor Unes may be compared and the one having the lowest value may be selected on the theory that, if a finger or other object is proximate to the sensor a ⁇ ay, it wdl not be present at sensor lines located at the opposite edges of die a ⁇ ay.
- an "edge motion" feature may be implemented when die object position sensor of the present invention is used as a computer cursor control device in place of a mouse.
- a practical problem arises in the use of computer mice or other cursor control devices when an attempt is made to move an object over a large distance on a computer screen. This problem is encountered when a small mouse pad is used with a computer mouse, or when an object position sensor of the kind described herein has a smaU touch sensor area.
- the edge motion feature of the present invention helps to eliminate the need to use “rowing,” or multiple strokes of the finger to move a large distance on the screen.
- a prior solution to the long-distance drag problem has been to provide an acceleration feature, i.e., a "ballistic" curve, where the gain varies as a function of finger speed, allowing die user to move long distances, albeit clumsdy, using a repeated finger swishing motion.
- This technique can be used with any variable-speed pointing device, for example, with a mouse on a mouse pad of limited size.
- Typical mouse driver software includes an adjustable acceleration feature (sometimes under a misleading name like "mouse speed").
- the system of the present invention can distinguish between die commonly used "cUck”, “double cUck” and “drag” mouse gestures.
- the single-click and double-cUck gestures are implemented in a mouse using the mouse to move the cursor to the object of interest on the computer screen and dien "clicking" once or twice a mouse button connected to an electrical switch in the mouse body.
- a significant advantage of die present invention is diat die need for mechanical switches is eliminated, and the single-click and double-cUck gestures are implemented in the present invention by moving the cursor to die object of interest and tiien tapping a finger tip once or twice on the selected object.
- the present system can easdy distinguish these gestures from the drag gesture in which the finger is placed on die touch sensor surface and dragged across the surface in a desired direction while maintaining contact with die surface.
- the edge motion feature of the object position sensor is implemented by motion unit 18 of FIG. 1 and works by defining two zones in die sensing plane 10 containing the touch sensor array 22.
- the sensing plane 10 is preferably divided into an inner zone 240 comprising most of the central portion of the surface of sensing plane 10 and an outer zone 242, typicaUy comprising a thin marginal area at the periphery of the sensor a ⁇ ay.
- the center of the sensing plane 10 may be described as the origin (X center , Y center ) a cartesian coordinate system.
- Those of ordinary skiU in the art wiU recognize however that the inner and outer zones could be of any shape.
- inner zone 240 is defined by the upper dashed Une Y 0 , right-hand dashed line
- Outer zone 242 is the region between the outer edges of the sensing plane 10 defined by Y max , -Y max - X a an d -X ma an ⁇ the outer borders of inner zone 240 defined by Y 0 , X 0 , -Y 0 , and -X Q .
- finger motions in the inner zone 240 are translated in die standard fashion into motion events to be sent to the host computer.
- the standard way to communicate mouse motion to a host computer may also be employed in the present invention to communicate finger motion to a host computer.
- ⁇ X die change in the X position of the finger
- ⁇ Y die change in the Y position of the finger
- X cur is the cu ⁇ ent X position of the finger
- X oId is the last reported X position of die finger
- Y cur is the current Y position of the finger
- Y old is the last reported Y position of the finger
- A is a "gain factor" which is commonly encountered in mouse cursor control applications.
- the host computer takes ( ⁇ X- ⁇ Y) events and moves the cursor by the indicated amount in each axis, thus reconstructing die finger position on the screen as the successive ⁇ X and ⁇ Y values are accumulated. So far, this is standard cursor control behavior where edge motion is not considered.
- the edge motion feature of the present invention when the finger is reported as being in the outer zone 242, the edge motion feature of the present invention may be enabled.
- the determination of whether the finger is in the outer zone is a simple determination:
- FIG. 12 Ulustrates a hardware embodiment for determining whether a finger is in the outer zone 242, but those of ordinary skid in the art wdl readdy recognize that this determination could readdy be made by performing one of a number of equivalent software routines. Such software routines are obvious and straightforward from die functions described herein.
- Circuit 244 includes digital comparators 246, 248, 250, and 252, which may be straightforwardly implemented by conventional logic.
- Comparator 246 puts out a tme signal when the quantity X ⁇ at one of its inputs is greater than the fixed quantity X 0 presented to its other input.
- Comparator 248 puts out a tme signal when the quantity X cur at one of its inputs is less tiian the fixed quantity -X 0 presented to its other input.
- Comparator 250 puts out a tme signal when the quantity Y cur at one of its inputs is greater than the fixed quantity Y 0 presented to its other input.
- Comparator 252 puts out a tme signal when the quantity Y cur at one of its inputs is less than the fixed quantity -Y 0 presented to its other input.
- edge motion aspect of the present invention may be selectively enabled or disabled by a user.
- X center is the X coordinate of the center of the pad
- S is a multiplicative factor for speed. S should be chosen such that the movement of the cursor is at a comfortable speed on the display screen.
- die multipUcative speed factor S is set to be to be 3/4 as large as the multipUcative speed factor S ⁇ >
- edge motion feature of the present invention can be confusing if the user does not expect it. Since edge motion is most useful in connection witii the drag gesture, it is presently prefe ⁇ ed to a ⁇ ange for it to occur only during a drag, i.e., only when me gesture logic is virtually "holding die mouse button down.”
- the drag gesture and other gestures are implemented by gesture unit 20 of FIG. 1.
- the outer zone 242 "goes away” (i.e., is ignored) and the inner zone 240 effectively expands to cover the entire sensing plane 10. It has been found diat this is much less confusing in practice, probably because the user is more likely to be consciously aware of the cursor control device during a drag gesture than during simple cursor motions.
- FIG. 13 A hardware implementation of this algorithm is iUustrated in FIG. 13 in schematic diagram form. While circuit 256 is shown implemented in the X direction only, those of ordinary skill in the art wiU recognize diat an identical circuit wdl also be employed in die Y direction. Such skiUed persons wdl also immediately appreciate the complete equivalence of implementing die hardware solution of FIG. 13 as a software routine.
- Edge-motion circuit 256 includes a subtractor circuit 258 in which the previous value of X cur , stored in delay 260, is subtracted from the present value of X cur .
- the ou ⁇ ut of subtractor circuit 258 is presented to multipUer 262, which multipUes the result by the gain factor "A".
- the output of multipUer 262 is die term dX.
- X cur is also presented to subtractor circuit 264 in which the value of X cen -- r * s subtracted from the present value of X cur .
- the output of subtractor circuit 264 is presented to multiplier 266, which multiplies the result by d e gain factor "S".
- a two-input AND gate 268 has its input terms the value FingerOuter from the circuit of FIG.
- switch 270 is configured to pass the ou ⁇ ut of multiplier 266 to adder circuit 272. If either FingerOuter or MotionEnable is false, then switch 270 is configured to pass the value zero to adder 272.
- the output of switch 270 is the eX term.
- the output of adder 272 is passed to the host computer as
- the MotionEnable signal can be controlled by the user, e.g., by a control panel. Altematively, it may be controUed by the gesture unit as will be more fully disclosed.
- the dX term may be replaced by the eX term, and likewise for dY and eY, when die finger is in the "outer" zone, rather than adding the two terms in that zone. This results in a more "pure” edge motion which is harder for the user to guide. User tests have shown that the dX+eX form shown above feels better and is easier to use.
- the edge motion feature of the present invention is used advantageously with one or more finger gestures which may be performed by a user on the sensor a ⁇ ay and are recognized by the system.
- finger gestures which may be performed by a user on the sensor a ⁇ ay and are recognized by the system.
- the tap gesture is analogous to the cUcking of the mouse button on a conventional mouse, and the concept of dragging objects is famdiar to aU mouse users.
- the drag gesture consists of tapping once, foUowed by bringing the finger back down to die touch surface and moving it in the desired fashion.
- the host computer sees the virtual mouse button being held down during tiiis entire gesture.
- gesmre unit 20 detects the tap and drag gestures as follows. There are four state variables used to recognize the tap and drag gestures: TapState, NONE if there is no gesture in progress, TAP if a tap gesture is in progress, or DRAG if a drag gesture is in process; TapOkay, TRUE if high enough Z (finger pressure) has been seen to quahfy as a tap; DownTime, the time when the finger last touched down on the sensor pad; and DownPos, the starting (X,Y) position of the current tap.
- TapState NONE if there is no gesture in progress
- TAP if a tap gesture is in progress
- DRAG if a drag gesture is in process
- TapOkay TRUE if high enough Z (finger pressure) has been seen to quahfy as a tap
- DownTime the time when the finger last touched down on the sensor pad
- DownPos the starting (X,Y) position of the current tap.
- the parameters utihzed are: TapTime is the maximum duration of a tap gesture; DragTime is the maximum duration of a tap-and-drag gesture; TapRadius is the maximum distance moved during a tap gesture; Ztap is the minimum pressure (Z) for a tap gesture; and Zthresh is the minimum pressure (Z) to detect a finger.
- FIGS. 14a- 14c A process according to die present invention for recognizing tap and drag gestures is illustrated in the flow diagrams of FIGS. 14a- 14c.
- Processing begins at step 280 for every new set of (X,Y,Z) data to arrive from the arithmetic unit 16 of FIG. 1. In a cu ⁇ ent embodiment of the system, such data arrive 40 times per second.
- step 282 the Z (pressure) value is compared against the Z threshold Zthresh to determine whether a finger is present ("down") or not ("up").
- a simple threshold comparison two thresholds may be used to provide hysteresis as is well-known in the art.
- Step 290 records the position and die time at which the finger touched down.
- Step 292 initiaUzes the TapOkay flag, which records whether or not the Z (pressure) information ever exceeds the Ztap threshold during the current tap.
- step 294 the finger is known to be up.
- the previous Z is checked to see whether the finger was previously up or is just now being lifted from the pad.
- a finger-up transition has been detected.
- Various tests are made of the most recent finger-down period to see if it quaUfies as a tap. To quaUfy, the finger-down period must have short duration (CurTime minus DownTime must be less than TapTime), little or no motion (the distance from CurPos to DownPos must be less than TapRadius) , and sufficient peak finger pressure (TapOkay must be TRUE), in order to qualify.
- a smaU amount of motion may have occurred due to natural vibration of die finger and od er variations.
- This motion wdl have already been transmitted to die host, causing die cursor to drift shghtiy away from the intended target of the tap gesture.
- this spurious motion is replayed to the host in reverse in order to cancel it out.
- the motion may be sent in a single lump-sum packet or replayed packet by packet If die host computer is not expected to apply extreme non-linear gain ("ballistics") to die received packets, a simple lump-sum transmission will suffice.
- Steps 300 and 302 give special consideration to multiple taps. If a tap gesture is recognized, and a previous tap gesture (at this point a potential drag gesture) is pending, then one or more packets reporting a release of d e virtual mouse button are sent to the host. This prevents the virtual button presses resulting from the two taps from mnning together into a single long virtual button press.
- the special button-release packet may be accompUshed by sending an extra packet to the host, or by setting a flag to suppress the virtual mouse button for the next subsequent packet.
- Step 304 records that a tap gesture is now in progress.
- step 306 the finger is still away from the pad. If the finger has been away from the pad long enough so that the cu ⁇ ent tap gesture (if any) no longer qualifies to be extended into a drag (i.e., Curtime minus DownTime exceeds Drag Time), or if a drag gesture is pending (TapState is
- step 308 the current tap or drag is terminated in step 308 (causing the virtual mouse button to be released).
- Steps 310 and 312 compare Z against Ztap. If Z is ever greater than Ztap during a given finger- down period, the TapOkay flag is set.
- Steps 314, 316, and 318 cause die virtual mouse button to be pressed during a tap or drag gesture, and released at all other times.
- TapTime is a fraction of a second and may be adjusted by the user
- DragTime is approximately equal to TapTime
- TapRadius is approximately 5-10% of the pad widtii.
- FIG 15 a simpUfied block diagram of a host computer system 400 as used in accordance witii the present invention is shown.
- the host computer system 400 has a central processing unit (CPU) 402 controUed by an operating system 404.
- AppUcations 406, capable of being run by operating system 404 and CPU 402 are loaded into the memory of the host computer system 400 as is well known in the art.
- documents in the appUcations 406 as weU as features and controls of the appUcations 406 are displayed graphically in a window on a visual display 408.
- an apphcation 406 Many of the controls and features of an apphcation 406 are not provided by executable code (software) which is part of the application 406, but rather exists as pieces of software known in the art as a dynamically Unked Ubrary (DLL) 410 in the memory of the host computer system 400.
- DLL dynamically Unked Ubrary
- an application 406 accesses at mntime a DLL 410 for the desired feature or control through an operating system 404 facdity caUed a dynamic linker.
- the dynamic linker wiU link an appUcation 406 to any DLL 410 desired by die application 406, thereby adding die feature represented by the DLL 410 to the application 406 without the need for executable code for diat feature to be actuaUy included in the code for the application 406.
- DLL's 410 are provided by the operating system 404 for the use of applications 406.
- various versions of the operating system 404 are provided by the operating system 404 for the use of applications 406.
- Microsoft ® WindowsTM provide a rich set of standard DLL's for implementing most typical control and display functions. As a consequence, most appUcations are generaUy written to expect many controls and display functions to be DLL's.
- the DLL's wdl be located and linked by the dynamic linker in the operating system at runtime.
- Scrollbar One of the most common display functions provided operating systems as a DLL, and consequentiy implemented almost universally by appUcations through a DLL, is the scrollbar. Shown in FIG. 16 is a typical scrollbar 420 found in a graphical display. Usually, the scroUbar 420 is graphicaUy depicted along one edge of an application display window. Scrollbar 420 provides a means for moving through a document displayed in an application window, wherein die document is typically larger tiian can be displayed in its entirety in the window at one time. With the aid of the scrollbar 420, the apphcation user can move through the document incrementally either one line or approximately one page at a time or in large steps.
- the scroUbar 420 shown in FIG. 16 comprises several graphically depicted components. These include an elevator 422, a shaft 424, and up and down scroll a ⁇ ows 426 and 428, respectively.
- the elevator 422 is the central moving portion of the scroUbar 420.
- the elevator 422 is also commonly known in the art as the tab or thumb.
- the elevator 422 is positioned within the shaft 424 and the elevator 422 may be moved within the shaft 424 either by sUding the elevator 422 along the shaft 424 with a drag gesture, as described above, by positioning the cursor eidier above or below die elevator 422 in the shaft 424 and implementing a tap gesmre to move the elevator a single large step in the desired direction, or as in the present invent, by positioning the cursor over either of the up or down scroU a ⁇ ows 426 and 428 and implementing a drag gesture to activate either of the scroU a ⁇ ows 426 or 428.
- a drag gesture as described above, by positioning the cursor eidier above or below die elevator 422 in the shaft 424 and implementing a tap gesmre to move the elevator a single large step in the desired direction, or as in the present invent, by positioning the cursor over either of the up or down scroU a ⁇ ows 426 and 428 and implementing a drag
- the elevator 422 shows die relative location of the viewing window witiiin the document. For example, when the elevator 422 is near die top of the shaft 424 of scrollbar 420, me document in die viewing window is near the beginning, when the elevator 422 is near the bottom of the shaft 424 of scrollbar 420 the document in the viewing window is near the end. By moving the elevator 422 up and down in shaft 424, any portion of the document may be positioned in the viewing window.
- the position of the document in die viewing window wdl move either up or down by approximately the size of a single viewing window. It is also known in die art that when die cursor is positioned in the shaft 424 and a tap gesture is implemented, the position of the document in the viewing window will correspond to the relative position of the cursor on the shaft 424 where the tap gesture was made.
- the scroUing function when the cursor is position over either of the up or down scroll a ⁇ ows 426 and 428 and a drag gesmre is made, the scroUing function is implemented. Unlike the prior art, which implements the scroUing function at a constant rate, the present invention utilizes pressure information Z to vary the rate of the scrolling function according to the fmger pressure. Accordingly, when the user presses on a scroU a ⁇ ow firmly, the document wdl scroll quickly. When the user presses lightly, the scrolling would slow down or even stop. This enhancement to conventional scrolhng features makes navigation dirough documents easier and more natural.
- the host computer system keeps track of the position of the cursor on the graphical interface.
- the scroll a ⁇ ow is activated, usuaUy by depressing a mouse button, in a mouse driven system, the operating system sends a message to the application program.
- the apphcation receives the message and is Unked to the operating system DLL implementing the scroll a ⁇ ow function.
- the scroll a ⁇ ow is depressed, die document wiU be scrolled through the viewing window at a constant rate which is usuaUy set by the operating system.
- a scroll modifier unit 412 implemented in the prefened embodiment as a software driver loaded and running simultaneously with the operating system 404 on the host computer system 400, instructs the operating system 404 that all scroll a ⁇ ow messages are not to be sent to applications 406, but rather are to be sent to the scroll modifier unit 412.
- the scroU modifier unit 412 is implemented as a software driver, tiiose of ordinary skid in the wdl recognize that a hardware state machine is a known equivalent and would also be a reasonable implementation of the scroll modifier unit 412.
- the scroU modifier unit 414 has access to the Z pressure information sensed by the touchpad sensor 414. With the pressure information, the scroU modifier is able to modify the scroll messages being sent by the operating system 404 to the applications 406.
- FIG. 17 Shown in FIG. 17 is a flow chart according to die present invention.
- the host computer system polls the object position information suppUed from the touch pad sensor.
- the operating system determines that the position of the cursor is over the scroll anow and a drag gesture has been implemented, a scroU message is sent. It should be appreciated by those of ordinary skill in the art diat a virtual button implemented by a drag gesture may be implemented by other gestures as well. It should also be appreciated by those of ordinary skill in the art that using the position information to determine when the cursor is over the scroll anow is also well known.
- the scroll message which is sent by the operating system is sent to the scroU modifier unit as it has instructed the operating system to do.
- the scroll modifier unit modifies the scroU rate using the Z pressure information by making the scroU rate a function of the pressure information from the touchpad sensor.
- the scroll rate is Unearly proportional to the pressure information.
- the scroll message is then relayed to die application by the scroll modifier unit with a scroll rate which has been modified by the scroU modifier unit to be a function of the Z pressure info ⁇ nation.
- step 460 the application Unks to the DLL for the scroUing function using the dynamic linker, and the document is scrolled as a function of the Z pressure information.
- the increased sensitivity of the touch sensor system of the present invention aUows for a Ughter input finger touch which makes it easy for human use. Increased sensitivity also makes it easier to use other input objects, like pen styli, etc. Additionally this sensitivity aUows for a trade-off against a thicker protective layer, or different materials, which both aUow for lower manufacturing costs.
- the sensor electronic circuit employed in die present invention is very robust and cahbrates out process and systematic enors. It wdl process the capacitive information from the sensor and provide digital information to an extemal device, for example, a microprocessor.
- the senor of the present invention may be placed in a convenient location, e.g., below the "space bar" key in a portable computer.
- a convenient location e.g., below the "space bar” key in a portable computer.
- the thumb of the user may be used as the position pointer on the sensor to control the cursor position on the computer screen.
- the cursor may then be moved without the need for die user's fingers to leave the keyboard.
- this is similar to the concept of the Macintosh Power Book with it's trackball, however the present invention provides a significant advantage in size over the trackball.
- Extensions of tiiis basic idea are possible in that two sensors could be placed below die "space bar” key for even more feature control.
- the computer display widi it's cursor feedback is one small example of a very general area of application where a display could be a field of lights or LED's, an LCD display, or a CRT. Examples include touch controls on laboratory equipment where present equipment uses a knob/button/touch screen combination. Because of the articulating abihty of this interface, one or more of those inputs could be combined into one of the inputs described with respect to the present invention.
- Consumer Electronic Equipment (stereos, graphic equahzers, mixers) applications often utiUze significant front panel surface area for slide potentiometers because variable control is needed.
- the present invention can provide such control in one small touch pad location. As Electronic Home Systems become more common, denser and more powerful human interface is needed.
- the sensor technology of the present invention permits a very dense control panel. Hand-held TV/VCR/Stereo controls could be ergonomically formed and allow for more powerful features if this sensor technology is used.
- the sensor of the present invention can be conformed to any surface and can be made to detect multiple touching points, making possible a more powerful joystick.
- the unique pressure detection abtiity of the sensor technology of the present invention is also key to this apphcation.
- Computer games, "remote” controls (hobby electronics, planes) , and machine tool controls are a few examples of appUcations which would benefit from the sensor technology of the present invention.
- the sensor technology of the present invention can best detect any conducting material pressing against it.
- By adding a compressible insulating layer covered by a layer of conductive material on top of the sensor the sensor of the present invention may also indirectly detect pressure from any object being handled, regardless of its electrical conductivity.
Abstract
Description
Claims
Priority Applications (3)
Application Number | Priority Date | Filing Date | Title |
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EP96940319A EP0861462A1 (en) | 1995-11-13 | 1996-11-06 | Pressure sensitive scrollbar feature |
JP9518925A JPH11511580A (en) | 1995-11-13 | 1996-11-06 | Pressure-sensitive scroll bar function |
KR1019980702712A KR19990064226A (en) | 1995-11-13 | 1996-11-06 | Pressure Sensing Scroll Bar Features |
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US08/558,114 | 1995-11-13 | ||
US08/558,114 US5889236A (en) | 1992-06-08 | 1995-11-13 | Pressure sensitive scrollbar feature |
Publications (1)
Publication Number | Publication Date |
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WO1997018508A1 true WO1997018508A1 (en) | 1997-05-22 |
Family
ID=24228267
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
PCT/US1996/017862 WO1997018508A1 (en) | 1995-11-13 | 1996-11-06 | Pressure sensitive scrollbar feature |
Country Status (6)
Country | Link |
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US (1) | US5889236A (en) |
EP (1) | EP0861462A1 (en) |
JP (1) | JPH11511580A (en) |
KR (1) | KR19990064226A (en) |
CN (1) | CN1202254A (en) |
WO (1) | WO1997018508A1 (en) |
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WO1999045521A1 (en) * | 1998-03-06 | 1999-09-10 | Audiovelocity, Inc. | Multimedia linking device with page identification and active physical scrollbar |
WO1999057630A1 (en) * | 1998-05-01 | 1999-11-11 | Scientific-Atlanta, Inc. | Method and apparatus to increase functionality of a user input device |
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WO2001045123A1 (en) * | 1998-09-04 | 2001-06-21 | Armstrong Brad A | Remote controller with pressure sensitive buttons |
EP1202155A2 (en) * | 2000-10-30 | 2002-05-02 | Sony Computer Entertainment Inc. | Electronic device for controlling a cursor |
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GB2330670B (en) * | 1997-10-24 | 2002-09-11 | Sony Uk Ltd | Data processing |
US6529920B1 (en) | 1999-03-05 | 2003-03-04 | Audiovelocity, Inc. | Multimedia linking device and method |
WO2003058589A2 (en) | 2002-01-08 | 2003-07-17 | Koninklijke Philips Electronics N.V. | User interface for electronic devices for controlling the displaying of long sorted lists |
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Also Published As
Publication number | Publication date |
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US5889236A (en) | 1999-03-30 |
JPH11511580A (en) | 1999-10-05 |
EP0861462A1 (en) | 1998-09-02 |
KR19990064226A (en) | 1999-07-26 |
CN1202254A (en) | 1998-12-16 |
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