WO1999001925A1 - Procede et dispositif de commande de commutateurs dans un systeme de commande a structure variable, a frequence controlable - Google Patents
Procede et dispositif de commande de commutateurs dans un systeme de commande a structure variable, a frequence controlable Download PDFInfo
- Publication number
- WO1999001925A1 WO1999001925A1 PCT/FR1998/001390 FR9801390W WO9901925A1 WO 1999001925 A1 WO1999001925 A1 WO 1999001925A1 FR 9801390 W FR9801390 W FR 9801390W WO 9901925 A1 WO9901925 A1 WO 9901925A1
- Authority
- WO
- WIPO (PCT)
- Prior art keywords
- signal
- control
- looped
- filtering
- controllable frequency
- Prior art date
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Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
- H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
- H02M7/53875—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current with analogue control of three-phase output
-
- G—PHYSICS
- G05—CONTROLLING; REGULATING
- G05B—CONTROL OR REGULATING SYSTEMS IN GENERAL; FUNCTIONAL ELEMENTS OF SUCH SYSTEMS; MONITORING OR TESTING ARRANGEMENTS FOR SUCH SYSTEMS OR ELEMENTS
- G05B11/00—Automatic controllers
- G05B11/01—Automatic controllers electric
- G05B11/26—Automatic controllers electric in which the output signal is a pulse-train
- G05B11/30—Automatic controllers electric in which the output signal is a pulse-train using pulse-frequency modulation
Definitions
- the field of the invention is that of pulse modulation. More specifically, the invention relates to the control of the frequency and of the width of pulses for controlling switches, and in particular power switches. Its field of application is in particular that of control systems with variable structure (hysteresis control, direct torque control (in DTC angle: "Direct Torque Control”)) and pulse width and / or frequency modulations ( MLI).
- the source 11 can be continuous, single-phase or three-phase alternative.
- the power converter 12 performs the function of adapting the source to the type of supply necessary for the proper functioning of the load 13: constant continuous source transformed into a single-phase alternative source at variable frequency and amplitude; three-phase alternative source transformed into continuous source with variable amplitude;
- This source type conversion is managed by the command module 14.
- This module generally integrates two functions:
- Variable structure control systems are used more and more, compared to conventional controls. This technique is also known as sliding mode control or direct torque control (in English DTC; "Direct Torque Control”).
- FIG. 2 illustrates the case of a change of structure by switching a state feedback.
- the electrical system 21 receives the voltage from an amplifier 22 controlled by a setpoint voltage delivered by one or other of the modules K1 and K2 (23 ! And 23 2 ), as a function of the switch 24 controlled by the law of switching S (x) 25.
- FIG. 3 presents the case of a change of structure by switching at the level of the amplifier (power converter).
- the switching law S (x) then controls the switch 31, which delivers the voltage E m a x or E min selected.
- This command has the advantage of very fast dynamics and very good robustness to parametric variations. It is possible that the switching takes place at a very high frequency (theoretically infinitely high) so that the system works in slip mode.
- Parameters of this "frequency controller” are calculated according to the parameters of the system to be controlled; - decompose the "variable structure” regulator into two sub-regulators: one is deduced for a linearization of the model of the system to be controlled and the second is an image of the basic regulator. It imposes closed loop dynamics and robustness for small parametric variations.
- the source is of the DC voltage type (that is to say of non-zero average value, as opposed to an AC voltage)
- the load is a three-phase synchronous or asynchronous motor
- the power converter is a three-phase voltage inverter ( conversion of a constant DC voltage into three AC voltages with variable frequency and amplitude).
- the control module must slave the motor currents to three alternative references, for example sinusoidal.
- the error between the current referenced 41 and the measured current 42 is treated by a corrector 43.
- the control of the power switches 44 and 45 is obtained by comparing 46 the output of the regulator 43 and a triangular signal 47 of frequency very high compared to that of the reference currents (40 to 100 times, or even more).
- This type of control ensures a switching of the power switches at a constant frequency (frequency of the triangular modulation signal), but the ripple of the current is not controlled, depending on the parameters of the load and the operating point.
- the synthesis of the regulator is, in general, based on linear servo-controls, which introduces a phase shift inherent in linear transfer functions, unless you use a sophisticated corrector requiring a fairly powerful processor or a very complex analog card.
- the quality of the control is closely linked to the finesse with which the parameters of the system model have been determined.
- a second method used to make not very sensitive, with respect to the frequency of the currents, the performances of the servo-control consists in carrying out a change of base via a nonlinear transformation matrix (called Park transformation), which transforms the alternative quantities into continuous (constant) components in the new base. As the currents are continuous in this base, the correctors are determined to ensure good performance at zero frequency.
- Park transformation nonlinear transformation matrix
- This method makes it possible to get rid of the problem of the variable frequency of the references for the synthesis of the current regulators but the sensitivity to the parameters of the model of the system remains unchanged compared to the previous method.
- FIG. 5 The principle of control by hysteresis is illustrated in FIG. 5. It consists in maintaining by means of three comparators with hysteresis 51 (in the case of a three-phase system) the actual currents in the machine within a width band imposed, centered on the reference currents.
- the change in switching frequency can be a source of annoying audible noise.
- the invention particularly aims to overcome these drawbacks of the state of the art.
- the object of the invention is to provide a technique for controlling the switching of static converters in a control system with variable structure which is very insensitive to variations in the parameters of the system to be controlled, or even practically independent of these, as a first approximation.
- Another objective of the invention is to provide such a technique, which is simple and inexpensive to implement.
- the invention also aims to provide such a technique, which can be implemented on an integrated circuit.
- Another object of the invention is to provide such a technique which is compatible with any type of system, and in particular which can be implemented both in single-phase systems and in multi-phase systems.
- a method for controlling the durations and periods of conduction of at least one power switch in a system of variable structure control comprising at least one switch operable to deliver a given electrical signal corresponding to an electrical system, as a function of a control signal taking into account a reference input signal and a signal looped sampled at the output of said electrical system, method according to which an oscillation at a controllable frequency is applied to said control signal, obtained by the application of filtering on said looped signal, said filtering being defined so as to induce a phase shift of - 180 ° between the looped and filtered signal on the one hand, and the input signal of the electrical system on the other hand, at said controllable frequency.
- a modulation of the control signal is produced.
- the return chain jointly performs two functions: a servo function, since the control signal will follow the reference input signal, and an oscillation function, which makes it possible to limit to a maximum frequency given the switching of the switches.
- the invention also relates to devices for controlling at least one power switch implementing such a method.
- a device therefore comprises means for applying to said signal for controlling an oscillation at a controllable frequency obtained by applying filtering to said looped-back signal, said filtering being defined so as to induce a phase shift of -180 °. between the looped and filtered signal on the one hand, and the input signal of said electrical system on the other hand, at said controllable frequency.
- This result is obtained using a function placed between the output and the input of ampli ication means.
- it can be obtained using an analog electronic filter whose natural frequency is close to said controllable frequency.
- said controllable frequency can be substantially constant, or adjustable.
- said filtering means can for example comprise a filter with switched capacities.
- the device according to the invention can be applied both to single-phase systems and to polyphase systems.
- the device advantageously comprises, for each of the phases: - a filter of the looped signal, said filtering being defined so as to induce a phase shift of -180 ° between the looped and filtered signal on the one hand , and the input signal from the electrical system on the other hand, at said frequency controllable, and
- the low-pass filter supplying a first comparator and the high-pass filter supplying a second comparator, delivering said control signal.
- the device of the invention can be produced using analog means, which makes it possible to obtain a very fast and relatively inexpensive assembly.
- the device of the invention is installed in an integrated circuit. This is possible, due to the relative simplicity of implementing the invention. We can thus produce a single component, finding applications in many fields.
- the method, the device and the system of the invention do not require precise knowledge of the parameters of the load to be supplied.
- the approach of the invention requires at most, as a first approximation, knowledge of the order of the system to be controlled.
- the invention also relates, of course, to control systems with variable structure implementing such a device.
- FIG. 1 schematically illustrates a system for which the invention can be applied
- Figures 2 and 3 show two known embodiments of the control of a variable structure system corresponding respectively to a change of structure by switching a state feedback or by switching at the amplifier;
- FIG. 4 illustrates the principle of control by pulse width modulation, known per se;
- Figure 5 illustrates the principle of control by hysterisis, also known;
- Figures 6A and 6B schematically show the general principle of the invention, according to two possible layouts;
- Figure 7 illustrates the detailed theoretical structure of a system according to Figure 6;
- Figure 8 shows the model used to study the linear part of the system;
- Figures 9 to 12 are gain and phase BODE curves for the model of Figure 8;
- FIG. 13 shows the complete system according to the invention.
- Figure 14 illustrates the signals obtained with the system of Figure 13;
- FIG. 15 is an enlargement of a portion of Figure 14;
- FIG. 16 illustrates an exemplary implementation of the system of the invention.
- Figure 17 shows the signals found on the system of Figure 16.
- Figure 18 shows the spectrum of the current in the system load of Figure 16.
- FIG. 19 illustrates a simulation model for analyzing the attack of the modulator
- Figures 20 and 21 illustrate the signals obtained with the model of Figure 19;
- FIG. 22 presents the case of the application of the modulator in a control model of a DC motor
- FIG. 23 illustrates the currents recorded in the case of FIG. 22;
- FIG. 24 shows an embodiment of the invention intended for three-phase loads; Figures 25 and 26 illustrate the currents obtained in the case of Figure 24; .
- FIG. 27 shows another embodiment, for a phase, in the case of a polyphase load.
- FIGS. 6A and 6B illustrate the general principle of the invention.
- the load 61 to be supplied with electrical power conventionally receives this power from an amplifier 62, the power switches of which are controlled by the error signal 63.
- the novelty of the invention is mainly based on the generation of this error signal 63.
- the invention proposes a new technique of pulse modulation, presenting numerous advantages.
- This signal 63 is in fact obtained by the creation of an oscillation produced by the insertion of a filter 64 on the return chain, in the case of FIG. 6A.
- the signal 63 is therefore the difference between the reference signal 65 and the filtered signal 66.
- the filter 64 is placed before the amplifier 62.
- FIG. 7 illustrates the detailed theoretical structure of a system implementing the principle illustrated in FIG. 6. It therefore forms a modulator allowing the control of a strong low frequency current in an electric charge 71, as a function of a signal of reference 72, image of the current to be produced in this load.
- the input signal is therefore the reference current 72
- the output signal is the strong current 73 passing through the load 71.
- the direct chain is made up, from left to right, of the transfer functions R ⁇ 74, of a non-linear power voltage amplifier 75 and of the IF function 71.
- the return chain from right to left, consists of the transfer functions R ⁇ 76 and F2 77 and in fact plays two roles, jointly, which will be described later.
- the function R ⁇ 74 is a real and positive transimpedance.
- the FI 71 function is representative of the electric charge, which is expressed mathematically, first approximation, by a first order low pass type transfer function. It does not introduce phase shift at very low frequency. Its cut-off frequency is, in practice, a few hundred Hertz.
- the function F2 is representative of a second order low pass filter. It does not introduce phase shift at very low frequency. Its natural frequency is greater than a few kilo Hertz.
- the input 72 and output 73 signals, each attacking a transimpedance R ⁇ , the two inputs of the comparator 78 are physically homogeneous at voltages.
- the amplifier 75 is of the non-linear type. It receives a signal whose physical nature is therefore a voltage. It delivers on its output a voltage depending on the sign of that applied to the input.
- the comparator 78 located between the transfer function R ⁇ input 74 and the amplifier 75, plays two roles: that of error detector and that of phase shifter. These two roles will be explained later.
- the return chain is used jointly in two electronic functions.
- the return chain performs a feedback of the output 73 on the input of the X r of the comparator 78. It allows to obtain on the output 73 a signal to the image of the signal present on the positive input of the comparator, which is proportional, to the coefficient R ⁇ , to the input signal 72 of the modulator.
- the comparator 78 sees, on its negative input, a signal which continuously tends towards the signal applied to its positive input, said reference signal.
- the comparator associated with the return chain allows the control of the output current according to the input current.
- the return chain introduces a phase rotation of -180 degrees between the output of amplifier 75 and the negative input X r of comparator 78.
- This phase rotation is of course dependent and strongly influenced by the F2 filter 11.
- This phase rotation is 0 ° modulo 360 between the output of amplifier 75 and its input.
- This frequency is therefore, for the selected digital values, not very sensitive to the parameters of the electric charge.
- the non-linear amplifier 75 fulfills the gain condition.
- the oscillation conditions are respected.
- the system illustrated in FIG. 13, simultaneously controls the output current as a function of the low input frequency reference signal and controls the oscillation frequency f OSc -
- comparator 78 receives sinusoidal information.
- the reference current to be reproduced can be of any shape. The particular case described below applies to certain applications, of the sinusoidal type. It illustrates the points of analysis which will follow.
- the current I ref is therefore chosen sinusoidal:
- I ref I. sin (( s t) The following parameters are used to illustrate the following:
- the servo loop makes it possible to obtain a signal on the negative input of the comparator which tends permanently towards the signal applied to its positive input.
- the transimpedances Rr ref and R ⁇ being assumed to have identical values, the current I s constantly tends towards the reference current I ref -
- the signals, I Reference ref (171) of the amplifier output Vs (172), J s (173), V r back to the comparator (174), show this operation.
- a magnification of this figure allows to better visualize this result.
- the switches are located within a power inverter 201 supplied from the three-phase network 202, via a power rectifier 203.
- the modulator 204 is attacked by the reference signal 205 which is a voltage corresponding to the current to be reproduced multiplied by the value of the transimpedance R ⁇ of the sensor.
- the parameter R ⁇ already encountered in the theoretical analysis is the transimpedance of the current sensor.
- the "sampled” current, in the load supply line, is "amplified” by the coefficient, equal to R ⁇ , fixed here at 1.35V / A.
- the reference signal 211 of the modulator and the signal 212 downstream of the current sensor are presented in FIG. 17.
- a high amplitude line appears at 4490Hz (line number 3). With the other two lines on either side, there is a spectral group there indicating indirectly the average frequency of oscillation, therefore of consumption of the power switches.
- the simulation of the modulator's attack by a step shows that the modulator quickly tends towards the target current and that the oscillation frequency stabilizes at a given value.
- the simulation model, processed using appropriate software, is illustrated in Figure 19.
- the oscillation is not very sensitive to the electrical parameters of the load.
- the electrical parameters of the load 71 therefore need not be known. Only a very vague order of magnitude is necessary to fix the parameters of the F2 77 filter.
- a DC motor can be compared to an electromotive force associated with an inductance (L) and a resistance (R).
- the switched power source is symmetrical (+ E, -E)
- the equivalent voltage switched across the impedance (R, L) is asymmetrical.
- the command 261 Depending on the target speed, the command 261 generates the value of the reference current which must flow in the winding of the direct current machine (MCC) 262.
- MCC direct current machine
- a protection stage limits this current at start-up. This limit current is chosen arbitrarily, in the example which follows, at 5A.
- FIG. 23 illustrates the reference currents (271) and in the load (272).
- the modulator of the invention also adapts to three-phase loads. On a synchronous machine, a simulation of the operation from the block diagram in FIG. 24 is proposed.
- the control 281 develops the reference currents as a function of the reference speed 282, the speed 283 of the machine 285 and the measured currents 284 which have undergone a pre-treatment by filtering within the modulator itself.
- the control 281 does not know the electrical parameters of the machine 285. Neither does the modulator 286.
- the modulator can be limited to the dotted line 311.
- the modulator controls the oscillation frequency and delivers a filtered image of the currents measured at the first input comparator.
- the filter F2 11 can also be placed between the high-pass output of a combined filter 314 and the negative input of the second comparator 313, since this filter acts at high frequency.
- the filter F2 can also be placed between the output of the second comparator 313 and the input of the amplifier 75.
- the modulator can still be implemented entirely in analog electronics.
- the first comparator 312 can be produced in digital electronics with or without a processor.
- the signals to be processed by the possible processor are then of low frequencies.
- the decomposition of the input comparator into two comparators 312 and 313 makes it possible to compare the reference and return quantities pre-filtered in the two-phase benchmarks of Concoordia and Park, known in electrical engineering. It is thus possible to take advantage of an advantage of three-phase PWM, namely the overmodulation of the amplitudes of the voltages.
- the invention therefore proposes a structure employing a non-linear amplifier of the relay type without hysteresis, associated with two modules whose output / input functions correspond respectively to the system to be controlled (FI) and to the new module of the invention (F2).
- This structure is capable of slaving a reference signal whose arbitrary low frequency spectrum and of jointly controlling an oscillation of higher frequency superimposed on the slaved signal.
- This oscillation allows, according to the invention, the switching of one or more power switches used in the context of applications with or without back-electromotive force, single-phase or multi-phase.
Abstract
Description
Claims
Priority Applications (7)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US09/446,934 US6376935B1 (en) | 1997-07-01 | 1998-06-30 | Method and device for controlling switches in a control system with variable structure, with controllable frequency |
IL13375698A IL133756A (en) | 1997-07-01 | 1998-06-30 | Method and device for controlling switches in a control system with variable structure, with controllable frequency |
EP98935062A EP0992105B1 (fr) | 1997-07-01 | 1998-06-30 | Procede et dispositif de commande de commutateurs dans un systeme de commande a structure variable, a frequence controlable |
CA002295846A CA2295846C (fr) | 1997-07-01 | 1998-06-30 | Procede et dispositif de commande de commutateurs dans un systeme de commande a structure variable, a frequence controlable |
DE69820262T DE69820262T2 (de) | 1997-07-01 | 1998-06-30 | Verfahren und vorrichtung zur steuerung der schalter in einem steuersystem mit variabeler struktur und steuerbarer frequenz |
JP50652599A JP2002508150A (ja) | 1997-07-01 | 1998-06-30 | 制御可能周波数、変動構造式操作指令装置の中の切替器の操作指令装置と方法 |
AU84444/98A AU8444498A (en) | 1997-07-01 | 1998-06-30 | Method and device for controlling switches in a control system with variable structure, with controllable frequency |
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
FR97/08548 | 1997-07-01 | ||
FR9708548A FR2765746B1 (fr) | 1997-07-01 | 1997-07-01 | Procede et dispositif de commande de commutateurs pour regulation par modulation d'impulsions a frequence commandable |
Publications (1)
Publication Number | Publication Date |
---|---|
WO1999001925A1 true WO1999001925A1 (fr) | 1999-01-14 |
Family
ID=9508911
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
PCT/FR1998/001390 WO1999001925A1 (fr) | 1997-07-01 | 1998-06-30 | Procede et dispositif de commande de commutateurs dans un systeme de commande a structure variable, a frequence controlable |
Country Status (10)
Country | Link |
---|---|
US (1) | US6376935B1 (fr) |
EP (1) | EP0992105B1 (fr) |
JP (1) | JP2002508150A (fr) |
CN (1) | CN1115768C (fr) |
AU (1) | AU8444498A (fr) |
CA (1) | CA2295846C (fr) |
DE (1) | DE69820262T2 (fr) |
FR (1) | FR2765746B1 (fr) |
IL (1) | IL133756A (fr) |
WO (1) | WO1999001925A1 (fr) |
Cited By (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
TWI563356B (en) * | 2014-10-09 | 2016-12-21 | Mitsubishi Electric Corp | Control device and control method |
Families Citing this family (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US7282897B2 (en) * | 2004-07-15 | 2007-10-16 | Intersil Americas, Inc. | Apparatus and method for transient control in a multiphase switching power supply |
AT505965B1 (de) | 2007-10-17 | 2012-11-15 | Siemens Ag | Verfahren zum betreiben eines schaltnetzteils |
CN113033026B (zh) * | 2021-04-26 | 2022-03-15 | 上海交通大学 | 一种具有可观性保证的工业边缘感知方法 |
CN113341710B (zh) * | 2021-05-21 | 2023-06-13 | 北京理工大学 | 一种飞行器敏捷转弯复合控制方法和应用 |
Citations (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5543753A (en) * | 1994-06-22 | 1996-08-06 | Carver Corporation | Audio frequency power amplifiers with actively damped filter |
Family Cites Families (6)
Publication number | Priority date | Publication date | Assignee | Title |
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FR2339274A1 (fr) * | 1976-01-23 | 1977-08-19 | Cem Oerlikon Traction | Procede et dispositif de recharge d'une source autonome d'energie embarquee a bord de vehicules electriques |
US4965532A (en) * | 1988-06-17 | 1990-10-23 | Olympus Optical Co., Ltd. | Circuit for driving ultrasonic transducer |
US5059924A (en) * | 1988-11-07 | 1991-10-22 | Level One Communications, Inc. | Clock adapter using a phase locked loop configured as a frequency multiplier with a non-integer feedback divider |
US5294769A (en) * | 1990-10-03 | 1994-03-15 | Daihen Corporation | Electric joining method of material including ceramics |
US6112125A (en) * | 1995-03-08 | 2000-08-29 | Silicon Systems, Inc. | Self-tuning method and apparatus for continuous-time filters |
US6208183B1 (en) * | 1999-04-30 | 2001-03-27 | Conexant Systems, Inc. | Gated delay-locked loop for clock generation applications |
-
1997
- 1997-07-01 FR FR9708548A patent/FR2765746B1/fr not_active Expired - Fee Related
-
1998
- 1998-06-30 JP JP50652599A patent/JP2002508150A/ja not_active Ceased
- 1998-06-30 WO PCT/FR1998/001390 patent/WO1999001925A1/fr active IP Right Grant
- 1998-06-30 EP EP98935062A patent/EP0992105B1/fr not_active Expired - Lifetime
- 1998-06-30 DE DE69820262T patent/DE69820262T2/de not_active Expired - Fee Related
- 1998-06-30 AU AU84444/98A patent/AU8444498A/en not_active Abandoned
- 1998-06-30 CN CN98808524A patent/CN1115768C/zh not_active Expired - Fee Related
- 1998-06-30 US US09/446,934 patent/US6376935B1/en not_active Expired - Fee Related
- 1998-06-30 IL IL13375698A patent/IL133756A/xx not_active IP Right Cessation
- 1998-06-30 CA CA002295846A patent/CA2295846C/fr not_active Expired - Fee Related
Patent Citations (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5543753A (en) * | 1994-06-22 | 1996-08-06 | Carver Corporation | Audio frequency power amplifiers with actively damped filter |
Non-Patent Citations (2)
Title |
---|
NABAE A ET AL: "A NOVEL INVERTER WITH SINUSOIDAL VOLTAGE AND CURRENT OUTPUT", IEEE INDUSTRY APPLICATIONS SOCIETY ANNUAL MEETING, vol. 1, 9 October 1992 (1992-10-09), pages 867 - 871, XP000368886 * |
RASHIDI N H: "IMPROVED AND LESS LOAD DEPENDENT THREE-PHASE CURRENT-CONTROLLED INVERTER WITH HYSTERETIC CURRENT CONTROLLERS", IEEE TRANSACTIONS ON INDUSTRIAL ELECTRONICS, vol. 42, no. 3, 1 June 1995 (1995-06-01), pages 325 - 330, XP000506394 * |
Cited By (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
TWI563356B (en) * | 2014-10-09 | 2016-12-21 | Mitsubishi Electric Corp | Control device and control method |
Also Published As
Publication number | Publication date |
---|---|
FR2765746A1 (fr) | 1999-01-08 |
DE69820262T2 (de) | 2004-09-16 |
AU8444498A (en) | 1999-01-25 |
CN1115768C (zh) | 2003-07-23 |
CA2295846C (fr) | 2007-03-13 |
CN1268260A (zh) | 2000-09-27 |
FR2765746B1 (fr) | 1999-09-17 |
IL133756A (en) | 2003-12-10 |
DE69820262D1 (de) | 2004-01-15 |
EP0992105A1 (fr) | 2000-04-12 |
CA2295846A1 (fr) | 1999-01-14 |
US6376935B1 (en) | 2002-04-23 |
EP0992105B1 (fr) | 2003-12-03 |
JP2002508150A (ja) | 2002-03-12 |
IL133756A0 (en) | 2001-04-30 |
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