WO1999031809A1

WO1999031809A1 - Pragmatic trellis-coded modulation system and method therefor

Info

Publication number: WO1999031809A1
Application number: PCT/US1998/026797
Authority: WO
Inventors: Ronald D. Mccallister; Bruce A. Cochran; John M. Liebetreu
Original assignee: Sicom, Inc.
Priority date: 1997-12-16
Filing date: 1998-12-16
Publication date: 1999-06-24
Also published as: AU2200099A

Abstract

A pragmatic trellis-coded modulator (28) includes a parsing circuit (48) for converting input information bits (30) into uncoded information bits (51) and to-be-coded information bits (53), a convolutional encoding circuit (62) for convolutional converting each of the to-be-coded information bits processed therein per unit interval of time, and a mapping circuit (68) for mapping the uncoded and the convolutional encoded information bits to provide a quadrature signal defining mapped phase points.

Description

PRAGMATIC TRELLIS-CODED MODULATION SYSTEM AND METHOD THEREFOR

TECHNICAL FIELD The present invention relates generally to the field of digital communications.

More specifically, the present invention relates to pragmatic trellis-coded modulators for digital communications.

BACKGROUND ART Pragmatic trellis coded modulation (PTCM) employs primary and secondary modulation schemes. A first set of information bits being communicated is processed by the primary modulation scheme, and a second set of communicated information bits is processed by the secondary modulation scheme. Differential encoding may optionally be applied independently to the first and second sets of information bits to help a receiving decoder resolve rotational ambiguities. The secondary modulation scheme encodes the second set of information bits, which is optionally differentially encoded, with a strong error detection and correction code, such as the well known K=7, rate 1/2 "Viterbi" convolutional code (i.e., Viterbi encoding). The primary modulation scheme need not encode its subset of the information bits, other than the optional differential encoding. The resulting first and second sets of bits are then concurrently PSK or APSK mapped to generate quadrature components of a transmit signal.

The symbol data are conveyed through the phase (PSK) or amplitude and phase (APSK) relationships between the quadrature components of the transmit signal. The PSK or APSK mapping causes the phase constellation to be perturbed more by the primary modulation than by the secondary modulation.

PTCM has become popular because it allows a single convolutional encoder and decoder to achieve respectable coding gains for a wide range of bandwidth efficiencies (e.g., 1-6 b/s/Hz) and a wide range of higher order coding applications, such as 8-PSK, 16-PSK, 16-QAM, 32-QAM, etc. For lower order coding applications, such as QPSK or BPSK, PTCM offers no advantage because quadrature, complex communication signals provide two independent dimensions (i.e., I and Q) per unit baud interval with which to convey two or fewer symbols per unit interval.

APSK modulation achieves performance improvements over an otherwise equivalently ordered PSK modulation. A prior art sixteen phase-point, rectilinear, APSK (16-R-APSK) constellation 10 is shown in FIG. 1. Constellation 10 and other R- APSK modulations are conventionally referred to as quadrature amplitude modulation (QAM), but will be referred to herein using the generic term "R-APSK" to distinguish them from polar APSK (P-APSK) modulations, discussed below.

R-APSK constellations represent a special class of constellations where one set of symbols is conveyed independently of another set of symbols. In 16-R-APSK (i.e., 16- QAM), two symbols are communicated using I-axis constellation perturbations and two symbols are communicated using Q-axis constellation perturbations. Since the I and Q axes are orthogonal, the two sets of symbols have no influence over one another. PTCM has been adapted to R-APSK constellations with moderate success. Typically, one primary modulation symbol and one secondary modulation symbol are conveyed by perturbations about each of the I and Q axes. Unfortunately, conventional R-APSK constellations do not achieve rotationally invariant communication systems without accepting a tremendous degradation in performance (e.g., 4 dB). Without rotational invariance, the duration required for a decoder to achieve synchronization is much longer than with rotational invariance. When rotational invariance is sacrificed, conventional R-APSK constellations achieve acceptable performance, but performance is still not optimized.

FIG. 1 denotes a primary sub-constellation 12 included in the exemplary 16-R- APSK constellation 10. Each primary sub-constellation 12 shares a common data value for the second set of information bits being communicated (i.e., the secondary modulation). Those skilled in the art will appreciate that 16-R-APSK constellation 10 actually includes four primary sub-constellations 12. FIG. 1 further denotes a single minimum secondary Euclidean distance 14 and a single minimum primary Euclidean distance 16 for the 16-R-APSK example. Minimum secondary Euclidean distance 14 is the smallest distance between phase points in constellation 10. Minimum primary Euclidean distance 16 is the smallest distance between phase points in any given primary sub-constellation 12.

The value of these minimum distances has a large influence on respective secondary modulation and primary modulation performance. One reason R-APSK communication systems do not demonstrate better performance is believed to be that these distances result from discrete, independent I, Q values which dictate the positions of the phase points in 16-R-APSK constellation 10. For example, constellation 10 is achieved when phase points have I and Q coordinates consisting of all sixteen combinations of ±1 and ±3, scaled by a factor of 1/(3 V^~~2). Minimum secondary Euclidean distance 14 is 2/(3 V^~2), and minimum primary Euclidean distance 16 is

4/(3 V^~2). As a result, the performance of primary modulation is not balanced with that of secondary modulation unless signal-to-noise ratio is held at a single specific value, and overall performance suffers.

Furthermore, conventional applications of PTCM to R-APSK constellations provide an excessive number of phase points at the respective minimum distances from other phase points. For the example 16-R-APSK constellation 10 depicted in FIG. 1, four minimum primary Euclidean distance 16 exist for each of the four primary sub- constellations 12, resulting in a total of sixteen minimum primary Euclidean distance 16 in constellation 10. This large number of minimum primary Euclidean distances 16 causes primary modulation performance to suffer. Likewise, for the 16-R-APSK example depicted in FIG. 1, twenty-four minimum secondary Euclidean distances 14 exist in constellation 10. These twenty four minimum secondary Euclidean distances 14 operate in combination with the strength of a particular convolutional code to greatly influence secondary modulation performance. Moreover, R-APSK constellations are particularly undesirably when used on peak power limited channels, such as characterize satellite communications. As illustrated by FIG. 1 for a specific 16-R-APSK constellation, phase points reside in three concentric phase-point rings 18. Peak transmitter power is required to transmit phase points on the outer phase-point ring 18'. In random data, only 1/4 of the data are transmitted at this peak power. Accordingly, the peak power capability that must be provided in the transmitter is used to transmit only 1/4 of the data, resulting in an inefficient use of the peak power capability. In general, R-APSK constellations require an excessive number of phase-point rings 18 for a given number of phase points in the constellation, and this excessive number of phase-point rings 18 causes an inefficient use of transmitter power so that an undesirably low amount of power is transmitted per bit.

Moreover, transmitter amplifiers introduce AM-AM and AM-PM distortions in the signals they amplify. AM-AM distortions characterize non-linear amplitude variations in an amplifier output signal which occur as a function of input amplitude but are not explained by amplifier gain. AM-PM distortions characterize phase variations in an amplifier output signal which occur as a function of input amplitude. The use of an excessive number of phase-point rings 18 in R-APSK for a given number of phase points requires transmitter amplifiers to operate at an excessive number of input amplitude states and causes an excessive amount of AM-AM and AM-PM distortions. In theory, P-APSK constellations should have superior characteristics to R-APSK constellations, particularly in peak power limited channels. P-APSK constellations can be arranged so that a greater percentage of random data is transmitted using the peak power to achieve transmitter amplifier utilization efficiency. In addition, AM-AM and AM-PM distortions can theoretically be reduced if fewer rings are used to implement a phase constellation when compared to a R-APSK constellation having an equivalent number of phase points.

Unfortunately, conventional P-APSK constellations are not adapted to PTCM communication systems. Accordingly, such constellations have been proposed in either uncoded or in fully coded applications. Uncoded applications apply no convolutional coding to the communicated information bits, and fully coded applications apply convolutional coding to all communicated information bits. Uncoded applications are highly undesirable because they demonstrate significantly degraded performance when compared with equivalent pragmatic or fully coded applications. Fully coded applications are undesirable because they require the use of different convolutional encoders and decoders for different modulation orders.

DISCLOSURE OF INVENTION Accordingly, it is an advantage of the present invention that an improved pragmatic trellis-coded modulator and method for a data communication system are provided.

Another advantage of the present invention is that a phase point constellation is provided which is suitable for PTCM communication schemes.

Another advantage of the present invention is that a P-APSK constellation is provided which is suitable for use in peak power limited channels.

Another advantage of the present invention is that a P-APSK constellation is provided for which minimum primary sub-constellation Euclidean distances are maximized while the quantity of such distances is minimized.

Another advantage is that a PTCM data communication system and method are provided which rely upon dependent encoded symbols.

The above and other advantages of the present invention are carried out in one form by a pragmatic trellis-coded modulator. The modulator includes a parsing circuit, a convolutional encoding circuit coupled to the parsing circuit, and a polar amplitude phase-shift keyed (P-APSK) mapping circuit coupled to the parsing circuit and the convolutional encoding circuit. The parsing circuit parses input information bits into uncoded bits and to-be-coded bits. The convolutional encoding circuit produces at least two encoded bits for each encoded bit processed therein per unit interval of time. The P-APSK mapping circuit accepts, per unit interval of time, at least two uncoded bits from the parsing circuit and at least two encoded bits from the convolutional encoding circuit, maps the accepted information bits to a mapped phase point within a constellation of phase points arranged in at least two adjacent concentric rings, the outermost pair of which possesses a like predetermined number of phase points per ring, and provides a quadrature signal defining the mapped phase point.

BRIEF DESCRIPTION OF DRAWINGS

A more complete understanding of the present invention may be derived by referring to the detailed description and claims when considered in connection with the Figures, wherein like reference numbers refer to similar items throughout the Figures, and: FIG. 1 shows a sixteen phase-point, R-APSK constellation used in a prior art data communication system;

FIG. 2 shows a block diagram of a digital communication system configured in accordance with the teaching of the present invention; FIG. 3 shows a block diagram of a pragmatic trellis-coded modulator, as used in the communication system shown in FIG. 2;

FIG. 4 shows a sixteen phase-point, polar, amplitude phase-shift keyed, fully- rotationally-invariant (16-P-APSK-FRI) constellation produced by a first embodiment of a mapping circuit portion of the modulator shown in FIG. 3; FIG. 5 shows a sixty-four phase-point, polar, amplitude phase-shift keyed, fully- rotationally-invariant(64-P-APSK-FRI) constellation produced by a second embodiment of the mapping circuit portion of the modulator shown in FIG. 3;

FIG. 6 shows a sixty-four phase point, polar, amplitude phase-shift keyed, non- fully-rotationally-invariant (64-P-APSK-NFRI) constellation produced by a third embodiment of the mapping circuit portion of the modulator shown in FIG. 3;

FIG. 7 shows the 16-P-APSK-FRI constellation of FIG. 4 depicting secondary sub-constellations and minimum secondary Euclidean distances;

FIG. 8 shows the 64-P-APSK-FRI constellation of FIG. 5 depicting secondary sub-constellations and minimum secondary Euclidean distances; FIG. 9 shows the 64-P-APSK-NFRI constellation of FIG. 6 depicting secondary sub-constellations and minimum secondary Euclidean distances;

FIG. 10 shows the 16-P-APSK-FRI constellation of FIG. 4 depicting primary sub- constellations 00_B and 01_B, including minimum primary Euclidean distances therein;

FIG. 11 shows the 16-P-APSK-FRI constellation of FIG. 4 depicting primary sub- constellations 10_B and 1 1_B, including minimum primary Euclidean distances therein;

FIG. 12 shows the 64-P-APSK-FRI constellation of FIG. 5 depicting two of four primary sub-constellations; and

FIG. 13 shows the 64-P-APSK-NFRI constellation of FIG. 6 depicting two of four primary sub-constellations.

BEST MODE FOR CARRYING OUT THE INVENTION FIG. 2 shows a block diagram of a digital communication system 20 configured in accordance with the teaching of the present invention. System 20 receives input data 22 to be transmitted. In one embodiment of the present invention, concatenated coding is implemented. Accordingly, in this embodiment input data 22 is passed to an input of a Reed-Solomon or other block encoder 24. An output of Reed- Solomon encoder 24 couples to an input of an interleaver 26, and an output of interleaver 26 couples to an input of a pragmatic trellis coded modulation (PTCM) modulator 28. In another embodiment of the present invention, concatenated coding is omitted, and information bits are applied directly to PTCM modulator 28. For convenience, the data supplied to PTCM modulator 28 are referred to herein as information bits 30 regardless of whether concatenated coding is implemented. PTCM modulator 28 is discussed in more detail below in connection with FIGs. 3 through 11.

PTCM modulator 28 generates phase point data that may be in the form of a quadrature transmission signal 31 which is supplied to a transmitter 32. Transmitter 32 couples to a transmission antenna 34 from which a digital communication signal 36 is broadcast through a communication channel. As illustrated in FIG. 2, digital communication signal 36 is invariably mixed with and corrupted to some degree by noise 37 within the communication channel. The resultant corrupted digital communication signal 36' is received at a reception antenna 38 which couples to an input of a receiver 40. In the preferred embodiments, receiver 40 implements a carrier- coherent reception scheme. Receiver 40 produces rectilinear (i.e.. I and Q) or polar (i.e., ψ and M, not shown) quadrature components which are then supplied to a PTCM demodulator 42.

PTCM demodulator 42 generates estimates 43 of information bits 30. In one embodiment of the present invention, an output of PTCM demodulator 42 couples to an input of a deinterleaver 44, an output of which couples to an input of a Reed-Solomon or other block decoder 46, which produces output data 45. An output of Reed-Solomon decoder 46 indicating when valid data are being received is fed back to PTCM demodulator 42 to aid in achieving node synchronization (i.e., to determine frame timing). In another embodiment, deinterleaver 44 and Reed-Solomon decoder 46 are omitted, in which case information-bit estimates 43 are output data 45. Other node synchronization techniques known to those skilled in the art may be used to identify frame timing. FIG. 3 shows a block diagram of PTCM modulator 28, as used in digital communication system 20, in accordance with a preferred embodiment of the present invention. The following discussion refers to FIGs. 2 and 3.

A stream of information bits 30 is applied to an input of a parsing circuit 48. Parsing circuit 48 partitions information bits 30 between an output providing a primary stream 50 of uncoded bits 51 and an output providing a secondary stream 52 of to-be- coded bits 53.

In a preferred embodiment, discussed in greater detail below in conjunction with FIGs. 4-5, 7-8, and 10-11, PTCM modulator 28 produces a fully-rotationally-invariant quadrature output. In this embodiment, uncoded bits 51 from parsing circuit 48 are passed to a four-phase differential encoding circuit 54. Four-phase differential encoding circuit 54 encodes uncoded bits 51 into convolutionally-uncoded bits 51 ', which are then passed to P-APSK mapping circuit 68. Similarly, to-be-coded bits 53 from parsing circuit 48 are passed to a two-phase differential encoding circuit 56. Two-phase differential encoding circuit 56 encodes to-be-encoded bits 53 into to-be- convolutionally-coded bits 53', which are then passed to convolutional encoding circuit 62.

In an alternative preferred embodiment, discussed in greater detail below in conjunction with FIGs. 6 and 9, PTCM modulator 28 produces a non-fully-rotationally- invariant quadrature output. In this embodiment, differential encoding circuits 54 and 56 are omitted, and uncoded and to-be-coded bits 51 and 53 are passed directly from parsing circuit 48 to P-APSK mapping circuit 68 and convolutional encoding circuit 62, respectively.

FIG. 3 denotes uncoded bits 51 of primary bit stream 50 as data (d) with a subscript of "2" or "3", and to-be-coded bits 53 of secondary bit stream 52 as data (d) with a subscript of "1". As discussed in more detail below, PTCM modulator 28 applies secondary modulation to secondary bit stream 52 and primary modulation to primary bit stream 50.

The present invention may be adapted to operate over a wide variety of modulation formats and orders and to produce a wide variety of effective code rates. However, for the sake of clarity the below-presented discussion focuses on a preferred embodiment which adapts the present invention to a 16-P-APSK modulation format and order to achieve a 7/8 code rate. In other words, for every 3 data bits processed, 4 symbols are transmitted. Those skilled in the art will appreciate that puncturing schemes may be employed to provide other code rates, e.g., an effective code rate of 7/8 is readily achievable.

In the preferred 16-P-APSK, rate 7/8 embodiment, parsing circuit 48 routes four of every seven information bits 30 into primary bit stream 50 as uncoded bits 51 and three of every seven information bits 30 into secondary bit stream 52 as to-be-coded bits 53. In particular, every zeroth, third, and fourth information bit 30 is routed to secondary bit stream 52 while every first, second, fifth, and sixth information bit 30 is routed to primary bit stream 50, as indicated by data (d) superscripts in FIG. 3. These seven information bits 30 are distributed by parsing circuit 48 over a period equivalent to one unit interval of time 49. A single unit interval of time 49 is indicated between post-parse vertical dotted lines 58 in FIG. 3. A unit interval of time 49 is required by digital communication system 20 to communicate a single phase point. In this 16-P-APSK embodiment, four symbols are communicated by a single phase point per unit interval of time 49. In a 64-P-APSK embodiment, which is discussed below, six symbols are communicated by a single phase point per unit interval of time 49. Unit interval of time 49 represents the reciprocal of the baud rate. Over each unit interval of time 49, the relative phase of quadrature components of digital communication signal 36 (see FIG. 1) transitions from one set of phase data (i.e., one phase point) to another.

In a fully-rotationally-invariant preferred embodiment, during every unit interval of time 49, four-phase differential encoding circuit 54 processes two uncoded bits 51 and produces two convolutionally-uncoded bits 51' that remain uncoded except for the differential encoding applied through four-phase differential encoding circuit 54. A single unit interval of time 49 is indicated between pre-puncture vertical dotted lines 58' in FIG. 3. Differential encoding circuit 54 generates an output which represents the difference between the two information bits being processed during a current unit interval of time (tj) 49' and the two information bits processed in a preceding unit interval of time (t₀) 49". These information bits produced by differential encoding circuit 54 are referred to as symbols (s).

Also in the fully-rotationally-invariant preferred embodiment, two-phase differential encoding circuit 56 processes one to-be-coded bit 53 and produces one information bit that remains uncoded except for the differential encoding applied through differential encoding circuit 56. Differential encoding circuit 56 generates an output which represents the difference between the current information bit being processed during current unit interval of time (tj) 49' and the information bit processed during preceding unit interval of time (t₀) 49".

In a fully-rotationally-invariant preferred embodiment, an input of a convolutional encoding circuit 62 couples to an output of two-phase differential encoding circuit 56. In a non-fully-rotationally-invariant preferred embodiment, four-phase differential encoding circuit 54 and two-phase differential encoding circuit 56 do not exist, and the input of convolutional encoding circuit 62 couples to the secondary-stream output of parsing circuit 48. In the preferred embodiment, convolutional encoding circuit 62 implements a transparent, recursive, K=7, rate 1/2 convolutional ("Viterbi") encoder, but encoders having other parameters may also be used. Convolutional encoding circuit 62 may implement either a systematic or non-systematic code. Since convolutional encoding circuit 62 implements a rate 1/2 code, two symbols (s) are produced for each to-be- coded bit 53 received from parsing circuit 48 (through two-phase differential encoding circuit 56, if included). FIG. 3 denotes the two symbols produced for each information bit processed by using the subscripts "0" and "1".

Since convolutional encoding circuit 62 implements a transparent code, a linear relationship exists between the two outputs of convolutional encoding circuit 62. In other words, if identical data streams except for one complemented bit are presented to convolutional encoding circuit 62, then convolutional encoding circuit 62 will produce corresponding symbol pairs for the data streams in which either both symbols are inverted or neither symbol is inverted.

Optionally, when puncturing is employed, the outputs of convolutional encoding circuit 62 provide unpunctured-encoded information bits 63 to a puncture controller 64. Puncture controller 64 selectively removes predetermined unpunctured-encoded information bits 63 and appropriately restructures the secondary information-bit stream 52 by delaying certain other unpunctured-encoded information bits 63 as necessary, thus producing encoded information bits 69.

For the rate 7/8 example, two of unpunctured-encoded information bits 63 are punctured out of the secondary information-bit stream 52 during every two-unit-interval time period 47. As illustrated in FIG. 3 between pre-map vertical dotted lines 58", during first unit interval of time (to) 49", puncturing does not occur. The zeroth bit di of to-be-coded information bits 53 is converted by convolutional encoding circuit 62 into symbols si and s₀ of encoded information bits 69. Bits si and s₀ of encoded information bits 69 are concurrently output to puncture controller 64 from convolutional encoding circuit 62 during first unit interval of time (t₀) 49" of a two-unit-interval time period 47.

Puncturing does occur during second unit interval of time (tt) 49' of the two-unit- interval time period 47. As illustrated in FIG. 3 during first unit interval of time (to) 49", zeroth bit di of to-be-coded information bits 53 is converted by convolutional encoding

3 3 3 circuit 62 into bits s₀ and S_\ of unpunctured-encoded information bits 63, but bit Si is punctured out. Similarly, the fourth data bit dj is converted by convolutional encoding circuit 62 into bits si and so of unpunctured-encoded information bits 63, but bit s₀ is punctured out. Bit s₀ of unpunctured-encoded information bits 63 is delayed so that it is output concurrently with bit si from puncture controller 64 during the second unit interval of the two-unit-interval time period 47. Of course, a FIFO or other rate equalizing device (not shown) may be used by convolutional encoding circuit 62 and/or puncture controller 64 to accommodate the diverse number of encoding operations which occur in different unit intervals of time 49.

Accordingly, the output of puncture controller 64 is encoded information bits 69, and for the rate 7/8 embodiment, three information bits 30 are processed through convolutional encoding circuit 62 and puncture controller 64 over a two-unit-interval time period 47 to produce four symbols, i.e., encoded information bits 69. In other embodiments, other code rates may be achieved by extending the puncturing frame over different numbers of unit intervals of time 49 to puncture different fractions of the total number of unpunctured-encoded information bits 63 generated by convolutional encoding circuit 62.

In an alternate embodiment which has no puncturing, puncture controller 64 may be omitted, in which case the output of convolutional encoding circuit 62 is encoded information bits 69. One to-be-coded information bit 53 is processed through convolutional encoding circuit 62 per unit interval of time 49 to produce two encoded information bits 69.

So that PTCM modulator 28 can operate over a range of diverse puncturing rates, a PTCM encoder controller 66 couples to puncture controller 64 to provide a data set which defines a particular puncturing scheme to implement. In one embodiment (not shown), puncture controller 64 includes two shift registers which are loaded in parallel with a data set pattern from PTCM encoder controller 66 and which are clocked at twice the unit interval rate so that the data set patterns circulates therein. Puncture controller 64 also includes a multiplexer coupled to the output of convolutional encoding circuit 62 and controlled by the two shift registers. The multiplexer drives a FIFO memory. The data set patterns indicate which unpunctured-encoded information bits 63 to puncture out. Non-punctured unpunctured-encoded information bits 63 are loaded into the FIFO memory in the sequence defined by the data set and pulled out synchronously with the occurrence of unit intervals. However, those skilled in the art can devise alternate implementation techniques for puncture controller 64.

Uncoded bits 51 from the primary-stream output of parsing circuit 48, or from four-phase differential encoding circuit 54, if included, couple to primary stream

(uncoded) inputs of a polar, amplitude phase-shift keyed (P-APSK) mapping circuit 68. Similarly, encoded bits 69 from an output of convolutional encoding circuit 62 couple to secondary stream (encoded) inputs of mapping circuit 68. In particular, during current unit interval of time (tj) 49', 2^N"2 uncoded bits 51, (data bits d₃ and d₂, as symbol bits s₃ and s₂, in FIG. 3) drive the uncoded inputs of mapping circuit 68 in parallel and two encoded bits 69 (symbol bits s₀ and s₀ in FIG. 3) drive the encoded inputs of mapping circuit 68 in parallel, where N is the modulation order. The modulation order N equals four for the 16-P-APSK preferred embodiment depicted in FIG. 3 and equals six for the 64-P-APSK preferred embodiments discussed later. Accordingly, mapping circuit 68 maps four or more symbols per unit interval of time 49. P-APSK mapping circuit 68 implements a P-APSK phase point constellation arranged as discussed below. Mapping circuit 68 is desirably implemented as a random access memory (RAM) in which uncoded and encoded inputs represent memory address inputs. Thus, each mapping operation is performed by table look-up.

P-APSK mapping circuit 68 is configured to concurrently map uncoded bits 51 with encoded bits 69. One mapping occurs for each unit interval of time 49. Each mapping causes a phase point to be produced. Each phase point is characterized by quadrature components which exhibit a predetermined relative magnitude and phase. During a unit interval of time 49, a phase point is processed through transmitter 32 (FIG. 2) and conveyed to receiver 40 (FIG. 2). However, the inevitable presence of noise, transmitter distortions, receiver distortions, and other factors invariably causes receiver 40 to receive a somewhat different phase point than was transmitted. Accordingly, the arrangement of phase points in a phase point constellation has a significant influence on the ability of receiver 40 to successfully recover communicated data.

FIGs. 4 through 11 graphically illustrate P-APSK phase point constellations implemented by preferred embodiments of the present invention. FIG. 4 shows a 16- phase-point, polar, phase-shift keyed, fully-rotationally-invariant (16-P-APSK-FRI) constellation 70 produced by a first embodiment of P-APSK mapping circuit 68 (FIG. 3) in accordance with a preferred embodiment of the present invention. The following discussion refers to FIG. 4. 16-P-APSK-FRI constellation 70 includes phase points 72 arranged in an even number of concentric phase-point rings 74 of phase points 72. A single phase-point ring 74 includes the set of phase points 72 which have substantially equal magnitude.

16-P-APSK-FRI constellation 70 is derived from a QPSK constellation (not shown) for which pragmatic encoding has no benefit but which demonstrates desirable performance characteristics for uncoded or fully coded communications. A QPSK constellation (not shown) has a single ring of four phase points arranged 90° apart from adjacent phase points, implements a modulation order of two, and is used to communicate two symbols per unit interval.

16-P-APSK-FRI constellation 70 is derived from the QPSK constellation described above by providing four phase points 72 for each phase point in the original constellation. To do so, the QPSK ring is expanded into an outer (only) ring pair 75 having like numbers of phase points 72 per ring.

For outer ring pair 75, the original QPSK ring becomes an outer outer-pair ring 75' and an inner outer-pair ring 75" is added. One phase point 72 is added to outer outer- pair ring 75' for each of the four original phase points thereon to achieve a total of eight phase points 72. Two phase points 72 are provided on inner outer-pair ring 75" for each of the four original phase points on outer outer-pair ring 75' to achieve a total of eight phase points 72. All eight phase points 72 on each of outer outer-pair ring 75' and inner outer-pair ring 75" are uniformly distributed in phase, i.e., spaced 45° apart, with phase points 72 on inner outer-pair ring 75" being symmetrically interleaved with and substantially bisecting the phase angles of phase points 72 on outer outer-pair ring 75', i.e., rotated 22.5° with respect thereto.

FIG. 5 shows a sixty-four phase-point, polar, amplitude phase-shift keyed, fully- rotationally-invariant (64-P-APSK-FRI) constellation 70' produced by a second embodiment of P-APSK mapping circuit 68. The following discussion refers to FIG. 5. 64-P-APSK-FRI constellation 70' is derived from a 12/4, 16-P-APSK constellation (not shown) which is not well-suited to pragmatic encoding but which demonstrates desirable theoretical performance characteristics for uncoded or fully coded communications. Such a 12/4, 16-P-APSK constellation (not shown) has an outer ring of twelve phase points arranged 30° apart from adjacent phase points, an inner ring of four phase points arranged 90° apart, implements a modulation order of four, and is used to communicate four symbols per unit interval.

64-P-APSK-FRI constellation 70' is derived from the 12/4, 16-P-APSK constellation described above by providing four phase points 72 for each phase point in the original constellation. To do so, the two rings of the original constellation are expanded into an outer ring pair 75 and an inner ring pair 76, each of which has like numbers of phase points 72 per ring. For outer ring pair 75, the twelve-point outer ring of the original constellation becomes an outer outer-pair ring 75', and an inner outer-pair ring 75" is added. For outer outer-pair ring 75', one phase point 72 is added for each of the twelve original phase points to achieve a total of twenty-four phase points 72. For inner outer-pair ring 75", two phase points 72 are provided for each of the twelve original phase points on outer outer-pair ring 75' to achieve a total of twenty-four phase points 72. All twenty- four phase points 72 on each of outer and inner outer-pair rings 75' and 75" are uniformly distributed in phase, i.e., spaced 15° apart. Phase points 72 on inner outer- pair ring 75" are symmetrically interleaved with phase points 72 on outer outer-pair ring 75'. The phase angles of phase points 72 on inner outer-pair ring 75" substantially bisect the phase angles of phase points 72 on outer outer-pair ring 75', i.e., are rotated 7.5° with respect thereto.

For inner ring pair 76, the four-point outer ring of the original constellation becomes an outer inner-pair ring 76', and an inner inner-pair ring 76" is added. For outer inner-pair ring 76', one phase point 72 is added for each of the four original phase points to achieve a total of eight phase points 72. For inner inner-pair ring 76", two phase points 72 are provided for each of the four original phase points on outer inner- pair ring 76' to achieve a total of eight phase points 72. All eight phase points 72 on each of outer and inner inner-pair rings 76' and 76" are uniformly distributed in phase, i.e., spaced 45° apart. Phase points 72 on inner inner-pair ring 76" are symmetrically interleaved with phase points 72 on outer inner-pair ring 76'. The phase angles of phase points 72 on inner inner-pair ring 76" substantially bisect the phase angles of phase points 72 on outer inner-pair ring 76', i.e., are rotated 22.5° with respect thereto.

FIG. 6 shows a sixty-four phase-point, polar, amplitude phase-shift keyed, non- fully-rotationally-invariant (64-P-APSK-NFRI) constellation 70" produced by a third embodiment of P-APSK mapping circuit 68 (FIG. 3) in accordance with a preferred embodiment of the present invention. The following discussion refers to FIG. 6. 64-P-APSK-NFRI constellation 70" is derived from a 10/5/1, 16-P-APSK constellation (not shown) which is not well-suited to pragmatic encoding but which demonstrates desirable theoretical performance characteristics for uncoded or fully coded communications. Such a 10/5/1, 16-P-APSK constellation (not shown) has an outer ring often phase points arranged 36° apart from adjacent phase points, an inner ring of five phase points arranged 72° apart, a central "ring" of one phase point, implements a modulation order of four, and is used to communicate four symbols per unit interval. However, practical implementation of such a 10/5/1 constellation typically suffers due to the presence of the single phase point at the origin of the I and Q axes. Such a zero-magnitude signal typically results in significant transmitter or amplifier distortion.

64-P-APSK-NFRI constellation 70" is derived from the 10/5/1, 16-P-APSK constellation described above by providing four phase points 72 for each phase point in the original constellation. To do so, the three rings of the 10/5/1, 16-P-APSK constellation are expanded into an outer ring pair 75, an inner ring pair 76, and a central ring pair 77, each of which has like numbers of phase points 72 per ring.

For outer ring pair 75, the ten-point outer ring of the original constellation becomes an outer outer-pair ring 75', and an inner outer-pair ring 75" is added. For outer outer-pair ring 75', one phase point 72 is added for each of the ten original phase points to achieve a total of twenty phase points 72. For inner outer-pair ring 75", two phase points 72 are provided for each of the ten original phase points on outer outer-pair ring 75' to achieve a total of twenty phase points 72. All twenty phase points 72 on each of outer outer-pair ring 75' and inner outer-pair ring 75" are uniformly distributed in phase, i.e., spaced 18° apart. Phase points 72 on inner outer-pair ring 75" are symmetrically interleaved with phase points 72 on outer outer-pair ring 75'. The phase angles of phase points 72 on inner outer-pair ring 75" substantially bisect the phase angles of phase points 72 on outer outer-pair ring 75', i.e., are rotated 9° with respect thereto. For inner ring pair 76, the five-point outer ring of the original constellation becomes an outer inner-pair ring 76', and an inner inner-pair ring 76" is added. For outer inner-pair ring 76', one phase point 72 is added for each of the five original phase points to achieve a total often phase points 72. For inner inner-pair ring 76", two phase points 72 are provided for each of the five original phase points on outer inner-pair ring 76' to achieve a total of twenty phase points 72. All ten phase points 72 on each of outer and inner inner-pair rings 76' and 76" are uniformly distributed in phase, i.e., spaced 36° apart. Phase points 72 on inner inner-pair ring 76" are symmetrically interleaved with phase points 72 on outer inner-pair ring 76'. The phase angles of phase points 72 on inner inner-pair ring 76" substantially bisect the phase angles of phase points 72 on outer inner-pair ring 76', i.e., are rotated 18° with respect thereto. For central ring pair 77, the single central phase point of the original constellation becomes an outer central-pair ring 77', and an inner central-pair ring 77" is added. For outer central-pair ring 77', one phase point 72 is added to the original phase point to achieve a total of two phase points 72. For inner central-pair ring 77", two phase points 72 are provided for the original phase point on outer central-pair ring 77' to achieve a total of two phase points 72. Both phase points 72 on each of outer and inne^r central- pair rings 77' and 77" are uniformly distributed in phase, i.e., spaced 180° apart. Phase points 72 on inner central-pair ring 77" are symmetrically interleaved with phase points 72 on outer central-pair ring 77'. The phase angles of phase points 72 on inner central- pair ring 77" substantially bisect the phase angles of phase points 72 on outer central- pair ring 77', i.e., are rotated 90° with respect thereto.

Referring to FIGs. 4, 5, and 6, outer outer-pair ring 75' in constellation 70, 70', or 70", has a maximum number of phase points 72 possible for the desired signal performance (discussed elsewhere). Each subsequent phase-point ring 74 inward has a number of phase points 72 either equal to the number of phase points 72 on the next- outward phase-point ring 74 or an integer factor thereof. 16-P-APSK-FRI constellation 70 (FIG. 4) has one ring pair 75 in an 8/8 arrangement of phase points 72. 64-P-APSK- FRI constellation 70' has two ring pairs 75 and 76 in a 24/24/8/8 arrangement of phase points 72, eight being an integer factor of twenty-four. 64-P-APSK-NFRI constellation 70" has three ring pairs 75, 76, and 77 in a 20/20/10/10/2/2 arrangement of phase points 72, ten being an integer factor of twenty and two being an integer factor often.

Where inner outer-pair ring 75" is adjacent to outer inner-pair ring 76', phase points 72 on inner outer-pair ring 75" are symmetrically interleaved with phase points 72 on outer inner-pair ring 76'. Since the number of phase points 72 on outer inner-pair 76' is an integer factor of the number of phase points on inner outer-pair ring 75", not every adjacent pair of phase points 72 on inner outer-pair ring 75" will have an interleaved phase point 72 on outer inner-pair 76'. The phase angles of phase points 72 on outer inner-pair ring 76' substantially bisect the phase angles of those adjacent phase points 72 on inner outer-pair ring 75" that are so interleaved. A similar circumstance occurs in 64-P-APSK-NFRI constellation 70" between inner inner-pair ring 76" and outer central-pair ring 77'. Referring to FIGs. 4, 5, and 6, preferred labeling schemes are applied to phase points 72. The labeling schemes define primary and secondary sub-constellations. For constellations 70 and 70', the labeling schemes cooperate in achieving rotational invariance, which is discussed below.

The preferred labeling schemes are a set of binary codes in which a unique binary code is associated with each phase point 72. By applying the indicated binary code to inputs of P-APSK mapping circuit 68 (FIG. 3), the indicated phase point is produced. Likewise, when receiver 40 (FIG. 2) receives a phase point near those phase points indicated in FIGs. 4, 5, and 6, PTCM demodulator 42 (FIG. 2) desirably generates data estimates corresponding to the indicated binary codes. The preferred labeling schemes denote two bits to the right of a radix point and 2^N"

² bits to the left of the radix point for each binary code, where N equals the modulation order. The modulation order is four for 16-P-APSK-FRI constellation 70, six for 64-P- APSK-FRI constellation 70', and six for 64-P-APSK-NFRI constellation 70". The bits to the right of the radix point indicate encoded bits 69, i.e., secondary bit stream 52, and the bits to the left of the radix point indicate uncoded bits 51, i.e., primary bit stream 50. However, the radix point has no significance other than distinguishing encoded bits 69 from uncoded bits 51. Nothing requires encoded bits 69 and uncoded bits 51 to be in any particular order relative to each other. Rather, all encoded and uncoded bits 69 and 51 are independent of each other. While encoded and uncoded bits 69 and 51 for constellations 70, 70', and 70" are independent of each other, the resulting phase point symbols into which the information bits are mapped by P-APSK mapping circuit 68 are not independent from one another in order to achieve desirable performance characteristics.

FIGs. 7, 8, and 9 show constellations 70, 70', and 70", respectively, of FIGs. 4, 5, and 6, respectively, depicting secondary sub-constellations and minimum secondary Euclidean distances in accordance with preferred embodiments of the present invention. FIGs. 7, 8, and 9 omit the labeling denoted in FIGs. 4, 5, and 6, respectively, for clarity, but this labeling defines the secondary sub-constellation groupings of phase points 72 and will be understood to apply to FIGs. 7, 8, and 9. The following discussion refers to FIGs. 4 through 9. Each constellation 70, 70', or 70" has 2 ^' secondary sub-constellations 78, where

N equals the modulation order. Desirably, phase points 72 are clustered together in secondary sub-constellations 78 so that secondary sub-constellations 78 do not overlap, though those skilled in the art will appreciate that this is not a requirement of secondary sub-constellations 78. As a consequence of this, the center of each secondary sub- constellation 78 is not centered at the origin of constellation 70, 70', or 70".

Secondary sub-constellations 78 are formed from those phase points 72 that have common data values for their uncoded bits 51. Constellations 70, 70', and 70" have similar secondary sub-constellation 78 features which lead to desirable performance characteristics. For example, the labeling applied to phase points 72 causes for each secondary sub-constellation 78 to include two phase points 72 having a greater magnitude and two phase points 72 having a lesser magnitude. That is, for a given secondary sub-constellation 78, two phase points 72 are located on outer ring 75', 76', or 77' and two phase points 72 on inner ring 75", 76", or 77" of ring pair 75, 76, or 77, respectively. For a given magnitude within each secondary sub-constellation 78, one phase point 72 exhibits a first phase angle and another phase point 72 exhibits a second phase angle. These first and second phase angles differ from one another by the same offset angle. For 16-P-APSK-FRI constellation 70, that offset is 45° for phase points 72 on both outer and inner outer-pair rings 75' and 75". For 64-P-APSK-FRI constellation 70', that offset angle is 15° for phase points 72 on both outer and inner outer-pair rings 75' and 75", and 45° for phase points 72 on both outer and inner inner-pair rings 76' and 76". For 64-P-APSK-NFRI constellation 70", that offset is 18° for phase points 72 on both outer and inner outer-pair rings 75' and 75", 36° for phase points 72 on both outer and inner inner-pair rings 76' and 76", and 180° for phase points 72 on both outer and inner central-pair rings 77' and 77". The phase angles of phase points 72 on outer ring 75', 76', or 77' of each given secondary sub-constellation 78 do not equal the phase angles of phase points 72 on inner ring 75", 76", or 77". In other words, the phase angles of phase points 72 on inner rings 75", 76", or 77" are offset relative to and substantially bisect the phase angles of phase points 72 on outer rings 75', 76', or 77', respectively, within each secondary sub- constellation 78. A benefit of this offset is improved performance achieved by spacing the inner-ring phase points 72 farther away from the outer-ring phase points 72.

However, the symbols or phase points produced by inputting independent encoded bits 69 to P-APSK mapping circuit 68 are dependent on one another. For example, the two encoded bits 69 that drive mapping circuit 68 are responsible for identifying one of four possible phase points 72 within a secondary sub-constellation 78 that has a given data value for uncoded bits 51. This one-of-four possible phase points 72 will have a specific phase angle and magnitude. Neither of the two driving encoded bits 69 exclusively controls the phase angle or magnitude parameter, or an I and Q parameter if represented in accordance with a rectilinear coordinate system, and the absolute distances between adjacent phase points 72 within a given secondary sub-constellation 78 will differ depending upon which two adjacent phase points 72 are being evaluated. For example, adjacent phase points 72 on the outer ring are farther apart than adjacent phase points 72 on the inner ring.

In other words, there are 2^N phase points 72 in constellation 70, 70', or 70", where N is the order of magnitude (i.e., the number of information bits 30 (FIG. 3) mapped by P-APSK mapping circuit 68 (FIG. 3) per unit interval of time 49 (FIG. 3). These 2^N information bits are divided into 2^N"2 secondary sub-constellations 78, where each secondary sub-constellation 78 has four phase points sharing a common data value for uncoded bits 51 (FIG. 3). Each of these constellation has 2^N"2 secondary sub- constellations 78 with two phase points at a first magnitude (i.e., on outer ring 75', 76', or 77' of ring pair 75, 76, or 77, respectively), and, because of a possible exception of central ring pair 77 (discussed later), at least no fewer than one less as many secondary sub-constellations 78, i.e., (2^N"2)-1, with two phase points 72 at a second magnitude (i.e., on inner ring 75", 76", or 77" of ring pair 75, 76, or 77, respectively).

FIGs. 7, 8, and 9 indicate a selection of candidates for minimum secondary Euclidean distances 80. Minimum secondary Euclidean distances 80 represent the distances between adjacent or otherwise nearby phase points 72 in constellations 70, 70', and 70". Of course, constellations 70, 70', and 70" can be characterized as having numerous other Euclidean distances between phase points 72, but these minimum secondary Euclidean distances 80 are particularly influential in controlling performance. In this context, performance refers to the resulting error rate that results from operating at a given signal-to-noise ratio, modulation order, and effective coding rate. The smaller the minimum secondary Euclidean distance 80, the worse the performance. However, this secondary modulation performance is compensated for by coding gain achieved through convolutional encoding. Accordingly, the code employed by convolutional encoding circuit 62 (FIG. 3) along with the relative magnitude of phase-point rings 74 for constellation 70, 70', or 70" define and establish the encoded-bit performance of digital communication system 20.

From a practical point of view, using outer ring pair 75 as an example, outer outer- pair ring 75' should contain as many points as possible in keeping with the desired performance characteristic. Since inner outer-pair ring 75" has the same number of phase points 72 as does outer outer-pair ring 75', the distance between adjacent phase points 72 on inner outer-pair ring 75" is minimum secondary Euclidean distance 80. To maximize performance, inner outer-pair ring 75" should be as close as possible to outer outer-pair ring 75' while maintaining the desired minimum secondary Euclidean distance 80. This occurs when phase points 72 on inner outer-pair ring 75" are positioned so as to substantially bisect the phase angles of phase points 72 of outer outer-pair ring 75 and the distance between phase points 72 on inner outer-pair ring 75" and adjacent phase points 72 on outer outer-pair ring 75' are substantially equal. That is, a phase-point triad 81 (FIG. 7), having two phase points 72 on inner outer-pair ring 75" and one phase point 72 on outer outer-pair ring 75', forms roughly an equilateral triangle. The same generalization holds true for inner ring pair 76 (FIGs. 8 and 9). Central ring pair 77 (FIG. 9) of 64-P-APSK-NFRI constellation 70" poses a slightly different problem. Phase points 72 on outer central-pair ring 77' are interleaved between and bisect the phase angles of phase points 72 on inner inner-pair ring 76" in a normal manner. The distance between either phase point 72 on outer central-pair ring 77' to either adjacent phase point 72 on inner inner-pair ring 76" is approximately equal to minimum secondary Euclidean distance 80 and determines the position of outer central-pair 77' relative to inner inner-pair ring 76".

Because phase points 72 on inner central-pair ring 77" are 90° away from phase points 72 on outer central-pair ring 77', phase points 72 on inner central-pair ring 77" are radially coincident to two of phase points 72 on inner inner-pair ring 76". The distances between these coincident phase points 72 are also approximately equal to minimum secondary Euclidean distance 80, and determine the position of inner central-pair ring 77" relative to inner inner-pair ring 76". This places outer and inner central-pair rings 77' and 77" in close proximity to each other. Since outer and inner central-pair rings 77' and 77" are so close together, they may be thought of as a single elliptical ring (not shown) instead of as two circular phase-point rings 74. From this point of view, 64-P- APSK-NFRI constellation 70" may be thought of as having a 20/20/10/10/4 phase-point configuration.

Minimum secondary Euclidean distances 80 are actually candidate distances because not all such distances actually need to be absolute minimum distances. As the relative magnitude of phase-point rings 74 changes, these distances change. As inner rings get larger relative to outer rings, then minimum secondary Euclidean distances 80 between adjacent phase points 72 on the inner rings increase while minimum secondary Euclidean distances 80 between adjacent phase points 72 on different rings decrease. If, for 16-P-APSK-FRI constellation 70, inner outer-pair ring 75" has a magnitude approximately 65 percent of outer outer-pair ring 75', then minimum secondary Euclidean distances 80 between adjacent phase points on a common ring equal minimum secondary Euclidean distances 80 between adjacent phase points 72 on adjacent rings. Desirably, several minimum secondary Euclidean distances 80 in constellation 70 are nearly equal, and minimum secondary Euclidean distances 80 are as large as possible. This is typically achieved when the magnitude of inner outer-pair ring 75" is in the range of 60-72 percent of the magnitude of outer outer-pair ring 75'.

FIGs. 10 and 11 show the 16-P-APSK-FRI constellation 70 (FIG. 4), with each of FIGs. 10 and 11 depicting two primary sub-constellations 82. FIGs. 10 and 11 also illustrate various primary Euclidean distances 84 therein. The following discussion refers to FIGs. 4, 10, and 11. Each of FIGs. 10 and 11 depict a single outer primary sub-constellation 82' and a single inner primary sub-constellation 82", with different primary sub-constellations 82 being depicted in FIGs. 10 and 11. Consequently, a total of four different primary sub- constellations 82 are collectively depicted in FIGs. 10 and 11. Primary sub- constellations 82 coexist with secondary sub-constellations 78 (FIGs. 7, 8, and 9) within a constellation implemented in P-APSK mapping circuit 68 (FIG. 3). The different sub- constellation 78 and 82 reflect different groupings applied to the same sets of phase points 72 by a preferred labeling scheme that causes a P-APSK constellation to accommodate pragmatic coding. For 16-P-APSK-FRI constellation 70, each of primary sub-constellations 82 encompasses those phase points 72 defined by like sets of encoded bits 69 (FIG. 3). In the preferred labeling scheme, phase points 72 having like sets of encoded bits 69 will have like digits to the right of the radix point (FIG. 4). Since there are two encoded bits 69 for any given phase point, there are four sets of digits, being 00_B, 01_B, 10_B, and 1 lβ, as seen in FIG. 4.

As seen in FIGs. 10 and 11 for 16-P-APSK-FRI constellation 70, each primary sub-constellation 82 resembles a square having vertices at phase points 72 spaced 90° apart at equal magnitudes. The four primary sub-constellations 82 are rotated multiples of 22.5° from one another, with phase points 72 of inner primary sub-constellations 82" being rotationally interspersed between phase points 72 of outer primary sub- constellations 82', bisecting the phase angles thereof.

Referring to FIGs. 5 and 12, FIG. 12 shows 64-P-APSK-FRI constellation 70' depicting two of four primary sub-constellations 82 in accordance with a preferred embodiment of the present invention. Each primary sub-constellation resembles a regular dodecagon encompassing a square. Outer primary sub-constellations 82' (only one of which is shown) have a dodecagon with vertices at phase points 72 spaced 30° apart on outer outer-pair ring 75', and a square with vertices at phase points 72 spaced 90° apart on outer inner-pair ring 76'. Similarly, inner primary sub-constellations 82" (only one of which is shown) utilize inner rings 75" and 76", respectively. For each primary sub-constellation, phase points 72 of the squares are rotationally interspersed between pairs of phase points 72 of the dodecagons, bisecting the phase angles thereof. The four primary sub-constellations are rotated multiples of 7.5° from one another, with phase points 72 of the inner sub-constellations being rotationally interspersed between phase points 72 of the outer sub-constellations.

Referring to FIGs. 6 and 13, FIG. 13 shows 64-P-APSK-NFRI constellation 70" depicting two of four primary sub-constellations 82 in accordance with a preferred embodiment of the present invention. Each primary sub-constellation resembles a regular decagon encompassing a regular pentagon encompassing an offset point. Outer primary sub-constellations 82' (only one of which is shown) have a decagon with vertices at phase points 72 spaced 36° apart on outer outer-pair ring 75', a pentagon with vertices at phase points 72 spaced 72° apart on outer inner-pair ring 76', and an offset point at a single phase point 72 on outer central-pair ring 77'. Similarly, inner primary sub-constellations 82" (only one of which is shown) utilize inner rings 75", 76", and 77", respectively. For each primary sub-constellation, phase points 72 of the pentagons are rotationally interspersed between pairs of phase points 72 of the decagons, bisecting the phase angles thereof, and the offset point is rotationally interspersed between a pair of phase points 72 of the pentagon, bisecting the phase angles thereof. The four primary sub-constellations are rotated multiples of 9° from one another, with phase points 72 of the inner sub-constellations being rotationally interspersed between phase points 72 of the outer sub-constellations. Referring to FIGs. 4 through 13, each primary sub-constellation 82 includes those phase points 72 that have common data values for their encoded bits 69. From the perspective of PTCM demodulator 42 (FIG. 2), when the data value of encoded bits 69 has been resolved to a high degree of confidence, the specific primary sub-constellation 82 defined by this resolved data value for the encoded bits 69 represents 2^N"2 data values that are potentially expressed by the uncoded bits 51 conveyed by the same phase point 72.

FIGs. 10 and 11 also show minimum primary Euclidean distances 84" for inner primary sub-constellations 82" and non-minimum primary Euclidean distances 84' for outer primary sub-constellations 82'. Non-minimum primary Euclidean distances 84' are significantly larger than minimum primary Euclidean distances 84". Accordingly, minimum primary Euclidean distances 84", rather than non-minimum primary Euclidean distances 84', exert a significant influence over the uncoded bit performance of 16-P-APSK-FRI constellation 70. As the magnitude of inner outer-pair ring 75" increases, minimum primary Euclidean distances 84" increase, and the uncoded bit performance of constellation 70 improves. As discussed above, however, that improvement may come at the cost of a decrease in encoded bit performance. As the magnitude of inner outer-pair ring 75" decreases, minimum primary Euclidean distances 84" decrease, and uncoded bit performance of constellation 70 deteriorates.

If the magnitude of inner outer-pair ring 75" is set at 67 percent of the magnitude of the outer outer-pair ring 75', minimum primary Euclidean distances 84" become precisely equal to minimum primary Euclidean distances 16 for conventional 16-R- APSK modulation (FIG. 1). However, unlike R-APSK modulations, fewer than one minimum primary Euclidean distance 84" per phase point 72 results from P-APSK constellations 70, 70', and 70", when the preferred constellation labeling scheme is used compared to one minimum primary Euclidean distance 16 (FIG. 1) per R-APSK phase point. In fact, only one-half of a minimum primary Euclidean distance 84" is provided per phase point 72 in preferred constellations 70, 70', and 70".

In other words, 2^N phase points 72 are grouped into each of four primary sub constellations 82, where N is the order of magnitude, i.e., the number of information bits 30 (FIG. 3) being mapped by P-APSK mapping circuit 68 (FIG. 3) per unit interval of time 49 (FIG. 3). Of these 2^N phase points 72 per primary sub-constellation 82, 2^N"2 have a common value for encoded bits 69 (FIG. 3).

There are 2^N primary Euclidean distances 84 in a given constellation, which is equal to the number of phase points 72 within that constellation, i.e., sixteen for 16-P- APSK-FRI constellation 70, and sixty-four each for constellations 70' and 70". Since there are four primary sub-constellations 82, two of which are outer primary sub- constellations 82' and two of which are inner primary sub-constellations 82", and since minimum primary Euclidean distances 84" are inner primary Euclidean distances 84, there are less than 2^N minimum primary Euclidean distances (actually 2 12) per constellation. This is in marked contrast to the prior art 16-R-APSK constellation 10 (FIG. 1) where there are sixteen phase points and sixteen minimum primary Euclidean distances. For 16-P-APSK-FRI constellation 70 shown in FIGs. 10 and 11, a total of eight minimum primary Euclidean distances 84" exists. Consequently, other factors being equal, constellations 70, 70', and 70" exhibit improved performance over their R-APSK counterparts. Referring back to FIG. 7, 16-P-APSK-FRI constellation 70 includes twenty-four candidates for minimum secondary Euclidean distance 80, which is the same number included in the corresponding prior art 16-R-APSK constellation 10 shown in FIG. 1. For comparison purposes, by operating the inner phase-point ring 74 at 67 percent of the magnitude of the outer phase-point ring 74, sixteen of these twenty-four distance candidates are only 2 percent less than the corresponding R-APSK minimum secondary Euclidean distances 14 (FIG. 1) while the remaining eight are 8 percent greater than the corresponding R-APSK minimum secondary Euclidean distances 14. As a result, when compared to a corresponding R-APSK constellation, operation of the inner phase-point ring 74 at 67 percent of the magnitude of the outer phase-point ring 74 yields improved performance.

However, those skilled in the art will appreciate that the present invention has no requirement that the inner phase-point ring 74 operate at precisely 67 percent of the magnitude of the outer phase-point ring 74. Rather, this 67 percent value is useful for comparison purposes with corresponding R-APSK constellations. In one preferred embodiment, a data set is loaded into P-APSK mapping circuit 68 (FIG. 3) that establishes the magnitude of inner phase-point ring 74 relative to that of outer phase- point ring 74. This relative magnitude of phase-point rings 74 desirably causes uncoded bit performance to approximately equal coded bit performance at a given signal-to-noise ratio. Referring back to FIGs. 3, 4, and 5, the preferred embodiment of PTCM modulator 28 is further configured to implement fully-rotationally-invariant P-APSK constellations 70 and 70'. Rotational invariance refers to an ability of receiver 40 (FIG. 2) to remain locked regardless of which of numerous potential phase points is currently being used by the receiver as a reference. This phenomenon is often referred to as a phase ambiguity. Differential encoding circuits 54 and 56 of PTCM modulator 28 support rotational invariance. Those skilled in the art will appreciate that differentially encoded data may be correctly and easily decoded whether or not it has been inverted. In addition, the binary labeling scheme applied to constellations 70 and 70', for each subject phase point 72, there exists two adjacent phase points 72 on the same phase-point ring 74, each of which is labeled to have a data value for its encoded bits 69 that is inverted from the data value for the encoded bits 69 for the subject phase point 72, i.e., encoded bits 69 of any two adjacent phase points 72 on the same phase-point ring 74 are mutually inverse in data value. As illustrated in FIGs. 4 and 7, a 45° offset, or any integer multiple thereof, in a phase reference for any secondary sub-constellation 78 causes encoded bits 69 to become inverted from their true values. This inversion is easily compensated through differential decoding. As will be understood from the below-presented discussion, if encoded bits 69 are detected in their inverted state, the resulting decisions regarding uncoded bits 51 yield results that are likewise easily compensated through differential decoding. As further illustrated in FIGs. 4 and 7, a 90° offset, or any integer multiple thereof, in a phase reference for any secondary sub- constellation 78 results in a phase point 72 having the same data value for encoded bits 69. For this situation the correct, non-inverted, encoded bits 69 are recovered in receiver 40. Errors in uncoded bits 51 due to the 90°, and integer multiples thereof, phase ambiguities are corrected through differential decoding in the receiver. A combination of differential encoding, an appropriate labeling scheme, and an appropriate distribution of phase points 72 are required for a constellation to be fully rotationally invariant. In the preferred embodiments, constellations 70 and 70', when used with differential encoding circuits 54 and 56, are fully rotationally invariant. An advantage of full rotational invariance is a minimization in data stream interruption between the loss and regain of signal phase synchronization in receiver 40 (FIG. 2), e.g., with constellations 70 and 70', resynchronization is achieved in a two-interval time period 47 after loss. The penalty is often some degradation in signal performance assuming all other parameters remain the same.

Without the use of differential encoding circuits 54 and 56, constellations 70 and 70' are not fully rotationally invariant. In such a case, the use of 64-P-APSK-NFRI constellation 70" (FIG. 6) is preferred, as constellation 70" exhibits a marked increase in signal performance over constellations 70 and 70'. Without full rotational invariance, phase ^synchronization after loss may take a multiplicity of unit intervals of time 49 after phase synchronization loss. Depending upon the type and criticality of data being communicated, such a time interval may be irrelevant. For example, in a digital television signal, this may represent only a fraction of a single scan line in a single frame, and, because of phosphor persistence, be virtually undetectable to the human eye.

The present invention has been described above with reference to preferred embodiments. However, those skilled in the art will recognize that changes and modifications may be made in these preferred embodiments without departing from the scope of the present invention. These and other changes and modifications which are obvious to those skilled in the art are intended to be included within the scope of the present invention.

Claims

CLAIMSWhat is claimed is:

1. A pragmatic trellis-coded modulator (28) comprising: a parsing circuit (48) configured to parse information bits (30) into uncoded bits (51) and to-be-coded bits (53); a convolutional encoding circuit (62) coupled to said parsing circuit (48) and configured to produce at least two encoded bits (69) for each encoded bit (53) processed therein per unit interval of time (49); and a polar amplitude phase-shift keyed (P-APSK) mapping circuit (68) coupled to said parsing circuit (48) and said convolutional encoding circuit (62) and configured to: accept at least two of said uncoded bits (51) from said parsing circuit (48) per unit interval of time (49); accept at least two of said encoded bits (69) from said convolutional encoding circuit (62) per unit interval of time (49); map said accepted uncoded and encoded bits (51 ,69) to a mapped phase point (72), said mapped phase point (72) being one phase point (72) within a phase-point constellation (70,70', 70") having a plurality of said phase points (72) arranged in at least two concentric phase-point rings (74), the outermost pair (75) of which possesses a like predetermined number of phase points (72) per ring(74); and provide a quadrature signal (31) defining said mapped phase point.

2. A pragmatic trellis-coded modulator (28) as claimed in claim 1 wherein said P-APSK mapping circuit (68) is configured to: accept an integer number "N" of said information bits (30) per unit interval of time (49), N-2 of which are said uncoded bits (51) and two of which are said encoded bits (69); and map said uncoded and encoded bits (51 ,69) to said mapped phase point (72) within said phase-point constellation (70,70',70"), said phase-point constellation (70,70',70") having 2^N of said phase points (72).

3. A pragmatic trellis-coded modulator (28) as claimed in claim 2 wherein: said 2^N phase points (72) within said phase-point constellation (70,70',70") are grouped into four primary sub-constellations (82); each of said primary sub-constellations (82) includes 2 ^"2 of said phase points (72) having a common data value for said encoded bits (69); said 2^N"2 phase points (72) within each of said primary sub-constellations (82) exhibit a plurality of primary Euclidean distances (84); a portion of said primary Euclidean distances (84) extends for a minimum primary Euclidean distance (84"); and said phase-point constellation (70,70',70") has less than 2^N minimum primary Euclidean distances (84").

4. A pragmatic trellis-coded modulator (28) as claimed in claim 3 wherein said 2^N phase points (72) are arranged so that said phase-point constellation (70,70',70") has approximately 2^N/2 minimum primary Euclidean distances (84").

5. A pragmatic trellis-coded modulator (28) as claimed in claim 2 wherein: said 2^N phase points (72) are grouped into 2^N"2 secondary sub-constellations (78) within said phase-point constellation (70,70',70"); each of said secondary sub-constellations (78) has four phase points (72) with a common data value for said uncoded inputs (51); each of said secondary sub-constellations (78) has two phase points (72) exhibiting a first magnitude; and at least (2^N"2)-1 of said secondary sub-constellations (78) have two phase points (72) exhibiting a second magnitude which differs from said first magnitude.

6. A pragmatic trellis-coded modulator (28) as claimed in claim 5 wherein, for each of said secondary sub-constellations (78): each of said first-magnitude phase points (72) exhibits one of two phase angles; each of said second-magnitude phase points (72) exhibits one of two phase angles; and said phase angles of said second-magnitude phase points (72) differ from said phase angles of said first-magnitude phase points (72).

7. A pragmatic trellis-coded modulator (28) as claimed in claim 6 wherein, for each of said secondary sub-constellations (78), a phase-angle difference between said phase angles of said first-magnitude phase points (72) approximately equals a phase- angle difference between said phase angles of said second-magnitude phase points (72).

8. A pragmatic trellis-coded modulator (28) as claimed in claim 2 wherein: said modulator (28) additionally comprises a first differential encoding circuit (54) coupled between said parsing circuit (48) and said P-APSK mapping circuit (68); said modulator (28) additionally comprises a second differential encoding circuit (56) coupled between said parsing circuit (48) and said convolutional encoding circuit (62); said phase-point constellation (70,70') is a fully-rotationally-invariant phase-point constellation (70,70'); and for each data value of said encoded bits (69) there exists four phase points (72) of substantially the same magnitude and having substantially equal phase angles between adjacent ones of said four phase points (72).

9. A pragmatic trellis-coded modulator (28) as claimed in claim 1 wherein said P- APSK mapping circuit (68) is configured to: accept an integer number "N" of said information bits (30) per unit interval of time (49), two of which are said encoded bits (69) and said phase-point constellation (70,70',70") has 2^N of said phase points (72); associate each of said 2^N phase points (72) with a data value for said encoded bits (69); and position said 2^N phase points (72) upon said concentric phase-point rings (74) so that said data values of said encoded bits (69) for any two adjacent phase points (72) upon each of said phase-point rings (74) are mutually inverse.

10. A pragmatic trellis-coded modulator (28) as claimed in claim 1 wherein: said P-APSK mapping circuit (68) is configured to accept four of said information bits (30) per unit interval of time (49), two of which are said uncoded bits (51) and two of which are said encoded bits (69); said phase-point constellation (70) has sixteen of said phase points (72); said phase-point constellation (70) comprises one pair (75) of said concentric phase-point rings (74), said one ring pair (75) having an outer ring (75') and an inner ring (75"); each of said outer and inner rings (75',75") comprises eight phase points (72) having substantially equal phase angles between each pair of adjacent phase points (72); and each of said phase points (72) within said inner ring (75") has a phase angle substantially bisecting said phase angles of adjacent phase points (72) in said outer ring (75').

11. A pragmatic trellis-coded modulator (28) as claimed in claim 1 wherein: said P-APSK mapping circuit (68) is configured to accept six of said information bits (30) per unit interval of time (49), four of which are said uncoded bits (51) and two of which are said encoded bits (69); said phase-point constellation (70') has sixty-four of said phase points (72); said phase-point constellation (70') comprises a first pair (75) of said concentric phase-point rings (74) and a second pair (76) of said concentric phase-point rings (74) within said first ring pair (75); each of said first and second ring pairs (75,76) comprises an outer ring (75',76') and an inner ring (75 ",76"); for said first ring pair (75), each of said outer and inner rings (75',75") comprises twenty-four phase points (72) having substantially equal phase angles between each pair of adjacent phase points (72); for said second ring pair (76), each of said outer and inner rings (76',76") comprises eight phase points (72) having substantially equal phase angles between each pair of adjacent phase points (72); and for each of said first and second ring pairs (75), each of said phase points (72) within said inner ring (75",76") has a phase angle substantially bisecting said phase angles of adjacent phase points (72) in said outer ring (75',76^╧ä).

12. A pragmatic trellis-coded modulator (28) as claimed in claim 1 wherein: said P-APSK mapping circuit (68) is configured to accept six of said information bits (30) per unit interval of time (49), four of which are said uncoded bits (51) and two of which are said encoded bits (69); said phase-point constellation (70") has sixty-four of said phase points (72); said phase-point constellation (70") comprises a first pair (75) of said concentric phase-point rings (74) and a second pair (76) of said concentric phase-point rings (74) within said first ring pair (75); each of said first and second ring pairs (75,76) comprises an outer ring (75',76') and an inner ring (75",76"); for said first ring pair (75), each of said outer and inner rings (75',75") comprises twenty phase points (72) having substantially equal phase angles between each pair of adjacent phase points (72); for said second ring pair (76), each of said outer and inner rings (76',76") comprises ten phase points (72) having substantially equal phase angles between each pair of adjacent phase points (72); and for each of said first and second ring pairs (75,76), each of said phase points (72) within said inner ring (75",76") has a phase angle substantially bisecting said phase angles of adjacent phase points (72) in said outer ring (75',76').

13. A pragmatic trellis-coded modulator (28) as claimed in claim 1 wherein: said phase-point constellation (70,70',70") comprises a first pair (75) of said adjacent concentric phase-point rings (74) and a second pair (76) of said adjacent concentric phase-point rings (74) within said first ring pair (75); each of said first and second ring pairs (75,76) comprises an outer ring (75',76') and an inner ring (75 ",76"); said inner and outer rings (75',75") of said first ring pair (75) possess a like number of phase points (72) per ring (74); said inner and outer rings (76',76") of said second ring pair (76) possess a like number of phase points (72) per ring (74), which number is an integer factor of said number of phase points (72) per ring in said first ring pair (75); and each of said phase points (72) within said outer ring (76') of said second ring pair (76) has a phase angle substantially bisecting said phase angles of adjacent phase points (72) in said inner ring (75") of said first ring pair (75).

14. A method for pragmatically encoding information bits (30) to be communicated at a rate of four or more symbols per unit interval of time (49), said method comprising the steps of: distributing a first portion (51) of said information bits (30) to a polar, amplitude phase-shift keyed (P-APSK) mapping circuit (68) and a second portion (53) of said information bits (30) to a convolutional encoding circuit (62), said first portion (51) comprising at least two information bits (30) per unit interval of time (49); convolutionally encoding said second portion (53) of said information bits (30) so that at least two encoded bits (69) are produced per unit interval of time (49); and mapping said first portion (51) of said information bits (30) and said encoded bits (69) in said P-APSK mapping circuit (68) so that said phase points (72) are arranged in at least two concentric phase-point rings (74) within a phase-point constellation (70,70',70"), wherein each of said phase-point rings (74) has a unique magnitude, and wherein the outermost pair (75) of said phase-point rings (74) possesses a like predetermined number of phase points (72) per ring (74).

15. A modulating method as claimed in claim 14 wherein said mapping step comprises the steps of: grouping 2^N, where "N" is an integer number, of said phase points (72) within said phase-point constellation (70,70',70") into four primary sub-constellations (82), wherein each of said primary sub-constellations (82) has a unique set of 2^N"2 phase points (72); structuring each of said primary sub-constellations (82) so that all phase points (72) included in each primary sub-constellation (82) have a common data value for said encoded bits (69); exhibiting, within each of said primary sub-constellations (82), a plurality of primary Euclidean distances (84) among said 2^N"2 phase points (72) in said primary sub- constellations (82), wherein a portion of said primary Euclidean distances (84) extend for a minimum primary Euclidean distance (84"); and assigning uncoded data values to said 2^N phase points (72) so that said phase-point constellation (70,70',70") has less than 2^N of said minimum primary Euclidean distances (84").

16. A modulating method as claimed in claim 15 wherein said assigning step assigns said 2^N phase points (72) so that said phase-point constellation (70,70',70") has approximately 2^N/2 of said minimum primary Euclidean distances (84").

17. A modulating method as claimed in claim 14 wherein said mapping step comprises the steps of: grouping 2^N' where "N" is an integer number, of said phase points (72) within said phase-point constellation (70,70',70") into 2^N"2 secondary sub-constellations (78), wherein each of said secondary sub-constellations (78) has a unique set of four phase points (72); structuring each of said secondary sub-constellations (78) so that all phase points (72) included in each secondary sub-constellation (78) have a common data value for said uncoded bits (51); exhibiting, within each of said secondary sub-constellations (78), two of said phase points (72) at a first magnitude and at two differing phase angles; exhibiting, within at least (2^N"2)-1 of said secondary sub-constellations (78), two of said phase points (72) at a second magnitude and at two differing phase angles; defining said phase angles of said second-magnitude phase points (72) to be different from said phase angles of said first-magnitude phase points (72); and establishing a phase-angle difference between said phase angles of said first- magnitude phase points (72) to be approximately equal to a phase-angle difference between said phase angles of said second-magnitude phase points (72).

18. A modulating method as claimed in claim 14 wherein: said method additionally comprises the step of differentially encoding, after said parsing step, said uncoded bits (51) into convolutionally-uncoded bits (51'); said method additionally comprises the step of differentially encoding, after said parsing step, said to-be-coded bits (53) into to-be-convolutionally-coded bits (53'); said uncoded bits (51) accepted by said P-APSK mapping circuit (68) are said convolutionally uncoded bits (51'); said encoding step encodes said to-be-convolutionally-coded bits (53') into said encoded bits (69); and said phase-point constellation (70,70') is a fully-rotationally-invariant phase-point constellation (70,70').

19. A pragmatic trellis-coded modulator (28) comprising: a parsing circuit (48) configured to parse information bits (30) into uncoded bits (51) and to-be-coded bits (53); a convolutional encoding circuit (62) coupled to said parsing circuit (48) and configured to produce at least two encoded bits (69) for each to-be-encoded bit (53) processed therein per unit interval of time (49); and a polar amplitude phase-shift keyed (P-APSK) mapping circuit (68) coupled to said parsing circuit (48) and said convolutional encoding circuit (62) and configured to: accept an integer number "N" of said information bits (30) per unit interval of time (49), N-2 of which are said uncoded bits (51) and two of which are said encoded bits (69); map said accepted uncoded and encoded bits (51 ,69) to a mapped phase point (72), said mapped phase point (72) being one phase point (72) within a phase-point constellation (70,70',70") having 2^N of said phase points (72) arranged in at least two concentric phase-point rings (74), the outermost pair (75) of which possesses a like predetermined number of phase points (72) per ring (74); associate each of said 2^N phase points (72) with a data value for said encoded bits (69); position said 2^N phase points (72) upon said concentric phase-point rings (74) so that said data values of said encoded bits (69) for any two adjacent phase points (72) upon each of said phase-point rings (74) are mutually inverse; and provide a quadrature signal (31) defining said mapped phase point (72).