WO2009156891A1 - Switch mode power supplies - Google Patents

Switch mode power supplies Download PDF

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Publication number
WO2009156891A1
WO2009156891A1 PCT/IB2009/052503 IB2009052503W WO2009156891A1 WO 2009156891 A1 WO2009156891 A1 WO 2009156891A1 IB 2009052503 W IB2009052503 W IB 2009052503W WO 2009156891 A1 WO2009156891 A1 WO 2009156891A1
Authority
WO
WIPO (PCT)
Prior art keywords
pulse
magnitude
voltage
switch
mode
Prior art date
Application number
PCT/IB2009/052503
Other languages
French (fr)
Inventor
Gert-Jan Koolen
Martin Vasterink
Original Assignee
Nxp B.V.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Nxp B.V. filed Critical Nxp B.V.
Publication of WO2009156891A1 publication Critical patent/WO2009156891A1/en

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4258—Arrangements for improving power factor of AC input using a single converter stage both for correction of AC input power factor and generation of a regulated and galvanically isolated DC output voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H05B45/382—Switched mode power supply [SMPS] with galvanic isolation between input and output
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B20/00—Energy efficient lighting technologies, e.g. halogen lamps or gas discharge lamps
    • Y02B20/30—Semiconductor lamps, e.g. solid state lamps [SSL] light emitting diodes [LED] or organic LED [OLED]
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • This invention relates to a switch mode power supply (SMPS) for energising a load such a light emitting diode (LED).
  • SMPS switch mode power supply
  • An SMPS for driving an LED usually operates directly from the rectified mains supply, often using a buck or flyback configuration, with the switch generating an energising pulse train.
  • Known control methods are pulse width control, fixed on time control and peak current control. Each has a particular characteristic, particularly regarding output current, input voltage and input power factor. The two most important control modes are pulse width control and peak current control.
  • pulse width control the pulse width of the energising pulse train is constant. This has the advantage of good power factor but has the disadvantage of a considerable ripple on the output current powering the LED, causing the latter to flicker.
  • peak current control the pulse current is monitored and each pulse is terminated when the input current reaches a predetermined threshold. This has the advantage of a smoother output current but has the disadvantage of a poor input power factor.
  • a switch mode power supply for driving a load, such as an LED, from an AC source
  • the power supply comprising a rectifying device for delivering an amplitude-varying rectified input voltage from the AC source, an inductive element for powering the load, a switch for repeatedly interrupting the application of the input voltage across the inductive element to create a train of current pulses across the inductive element, and a control circuit which controls the switch so that the pulse train is subjected to different control modes during different time intervals of each cycle of the rectified input voltage.
  • the pulse train is subjected to a pulse width control mode, in which the time duration of each pulse is controlled, during a time interval when the rectified voltage is below a threshold voltage, and wherein the pulse train is subjected to a peak current control mode, in which the magnitude of a current pulse through the inductive element is limited, during a time interval when the rectified voltage is above the threshold voltage.
  • a pulse width control mode in which the time duration of each pulse is controlled, during a time interval when the rectified voltage is below a threshold voltage
  • a peak current control mode in which the magnitude of a current pulse through the inductive element is limited, during a time interval when the rectified voltage is above the threshold voltage.
  • the duration of each pulse is constant during the pulse width control mode, and during the peak current control mode a pulse is terminated when the current magnitude reaches a threshold magnitude.
  • the control circuit may additionally comprise an oscillator and a bistable mode switch which is responsive to the magnitude of the input voltage, the oscillator governing the initiation of each pulse and the mode switch governing the termination of each pulse.
  • the mode switch may be controlled by a comparator responsive to the difference between the magnitude of the input voltage and a reference voltage the magnitude of which is capable of adjustment in order to adjust said threshold voltage so as to vary the relative durations of the control modes.
  • Figure 1 is a circuit diagram of a switch mode power supply forming a preferred embodiment of the invention
  • Figures 2a, 2b and 2c are graphs illustrating the operation of the power supply of Figure 1 ;
  • Figure 3 is a graph illustrating a modification.
  • the power supply delivers electrical power from an AC mains source 1 to an LED 2.
  • the supply comprises a bridge rectifier 3 which subjects the AC mains input to half-wave rectification to give a waveform similar to that of Figure 2a.
  • This amplitude-vary input voltage is applied across the primary winding 4 of a transformer 5, a transistor switch 6 and a resistor 7.
  • the secondary winding 8 of the transformer 5 powers the LED 2 through a diode 9 and a capacitor 10 so that a DC voltage is applied across the LED 2.
  • An oscillator 12 produces a high frequency saw-tooth waveform indicated at 13 in Figure 1.
  • the oscillator delivers a start signal to the set terminal of a flip-flop 14 which controls the transistor switch 6 in such a way that the transistor switch 6 is switched to a conducting state at the commencement of each cycle of the oscillator waveform.
  • a mode switch 15 resets the flip-flop 14, this causing the transistor switch 6 to switch a nonconducting state.
  • the flip-flop 14 causes the transistor switch 6 to switch on and off alternately in sequence, thereby creating a train of energising pulses which are applied across the primary winding 4 of the transformer 5.
  • a comparator 16 controls the mode switch 15.
  • a first input to the comparator 16 is the amplitude-varying rectified voltage and a second input is a Vseiect voltage that can be adjusted in magnitude.
  • the mode switch 15 When the rectified input voltage is less than V se iect, as detected by the comparator 16, the mode switch 15 imposes a first control mode on the pulse train, and when the input voltage is more than V se iect (as detected by the comparator 16) the mode switch imposes a second control mode on the pulse train. Reset of the flip-flop 14, and therefore opening of the transistor switch 6, is dependent upon whether the mode switch is imposing the first control mode or the second control mode.
  • the transistor switch 6 is opened at a time dependent on the magnitude of an input voltage V pw supplied to a comparator 17.
  • V pw an input voltage supplied to a comparator 17.
  • the duration of each pulse is the same so the pulse width is constant throughout the first control mode.
  • This first control mode prevails for the periods of time indicated at 18 and 19 in Figure 2a which is a plot of the current through the LED 2 against time.
  • the transistor switch 6 is opened when the voltage across the resistor 7 exceeds an input voltage V pea k fed to a comparator 20.
  • V pea k an input voltage
  • the maximum current in each cycle is limited, as indicated at 22 in Figure 2b which is also a plot of LED current against time.
  • Figure 2c and it this alternating sequence of modes which is imposed on the control circuitry by the mode switch 15.
  • Figure 2c shows two half-rectified waves, corresponding in duration to one cycle of the alternating mains source
  • Adjustment of the magnitude of the voltage V se iect adjusts the threshold voltage at which mode change over takes place so adjustment of the magnitude of V se iect varies the relative durations of the control modes. Further, adjustment of the voltage V pw alters the duration of each pulse during the pulse control mode and adjustment of the voltage V pea k controls the magnitude of the maximum current during the peak current control mode.
  • the comparator 20 has a time delay which has the effect of increasing the output current 23, with the result that the power factor is further improved.

Abstract

A switch mode power supply energises a light emitting diode (2) and has a control circuit which subjects an energising pulse train to control modes in alternate sequence. When the magnitude of a half-wave rectified input voltage is less than a threshold voltage, the pulse train is subjected to a pulse width control mode during which the time duration of each pulse is constant. When the magnitude of the half-wave rectified input voltage is more than the threshold voltage, the pulse train is subjected to a peak current control mode in which the magnitude of a current pulse is limited. Combination of the two modes in the time domain enables an effective compromise to be reached between the conflicting requirements of high power factor and low current ripple.

Description

DESCRIPTION
SWITCH MODE POWER SUPPLIES
This invention relates to a switch mode power supply (SMPS) for energising a load such a light emitting diode (LED).
An SMPS for driving an LED usually operates directly from the rectified mains supply, often using a buck or flyback configuration, with the switch generating an energising pulse train. Known control methods are pulse width control, fixed on time control and peak current control. Each has a particular characteristic, particularly regarding output current, input voltage and input power factor. The two most important control modes are pulse width control and peak current control. In pulse width control, the pulse width of the energising pulse train is constant. This has the advantage of good power factor but has the disadvantage of a considerable ripple on the output current powering the LED, causing the latter to flicker. Under peak current control, the pulse current is monitored and each pulse is terminated when the input current reaches a predetermined threshold. This has the advantage of a smoother output current but has the disadvantage of a poor input power factor.
Known controlling methods do not allow a compromise (that is a tradeoff between the merits and drawbacks of the various control methods) to be reached, a disadvantage which the invention aims to remedy.
According to the invention there is provided a switch mode power supply (SMPS) for driving a load, such as an LED, from an AC source, the power supply comprising a rectifying device for delivering an amplitude-varying rectified input voltage from the AC source, an inductive element for powering the load, a switch for repeatedly interrupting the application of the input voltage across the inductive element to create a train of current pulses across the inductive element, and a control circuit which controls the switch so that the pulse train is subjected to different control modes during different time intervals of each cycle of the rectified input voltage. By employing different control modes during different time intervals of each cycle of the rectified input voltage, a compromise can be reached between important conflicting parameters, for example input power factor and current ripple.
Preferably, the pulse train is subjected to a pulse width control mode, in which the time duration of each pulse is controlled, during a time interval when the rectified voltage is below a threshold voltage, and wherein the pulse train is subjected to a peak current control mode, in which the magnitude of a current pulse through the inductive element is limited, during a time interval when the rectified voltage is above the threshold voltage.
In the preferred embodiment to be described, the duration of each pulse is constant during the pulse width control mode, and during the peak current control mode a pulse is terminated when the current magnitude reaches a threshold magnitude.
The control circuit may additionally comprise an oscillator and a bistable mode switch which is responsive to the magnitude of the input voltage, the oscillator governing the initiation of each pulse and the mode switch governing the termination of each pulse.
The mode switch may be controlled by a comparator responsive to the difference between the magnitude of the input voltage and a reference voltage the magnitude of which is capable of adjustment in order to adjust said threshold voltage so as to vary the relative durations of the control modes. This facility enables a desired compromise to be reached between the conflicting requirements of a good input power factor and a low output current ripple. Embodiments of the invention will now be further described, by way of example, with reference to the accompanying drawings, in which:
Figure 1 is a circuit diagram of a switch mode power supply forming a preferred embodiment of the invention;
Figures 2a, 2b and 2c are graphs illustrating the operation of the power supply of Figure 1 ; and
Figure 3 is a graph illustrating a modification.
Referring to Figure 1 , the power supply delivers electrical power from an AC mains source 1 to an LED 2. The supply comprises a bridge rectifier 3 which subjects the AC mains input to half-wave rectification to give a waveform similar to that of Figure 2a. This amplitude-vary input voltage is applied across the primary winding 4 of a transformer 5, a transistor switch 6 and a resistor 7. The secondary winding 8 of the transformer 5 powers the LED 2 through a diode 9 and a capacitor 10 so that a DC voltage is applied across the LED 2.
An oscillator 12 produces a high frequency saw-tooth waveform indicated at 13 in Figure 1. The oscillator delivers a start signal to the set terminal of a flip-flop 14 which controls the transistor switch 6 in such a way that the transistor switch 6 is switched to a conducting state at the commencement of each cycle of the oscillator waveform. A mode switch 15 resets the flip-flop 14, this causing the transistor switch 6 to switch a nonconducting state. Thus, the flip-flop 14 causes the transistor switch 6 to switch on and off alternately in sequence, thereby creating a train of energising pulses which are applied across the primary winding 4 of the transformer 5. A comparator 16 controls the mode switch 15. A first input to the comparator 16 is the amplitude-varying rectified voltage and a second input is a Vseiect voltage that can be adjusted in magnitude.
When the rectified input voltage is less than Vseiect, as detected by the comparator 16, the mode switch 15 imposes a first control mode on the pulse train, and when the input voltage is more than Vseiect (as detected by the comparator 16) the mode switch imposes a second control mode on the pulse train. Reset of the flip-flop 14, and therefore opening of the transistor switch 6, is dependent upon whether the mode switch is imposing the first control mode or the second control mode.
In the first control mode, the transistor switch 6 is opened at a time dependent on the magnitude of an input voltage Vpw supplied to a comparator 17. Thus, the duration of each pulse is the same so the pulse width is constant throughout the first control mode. This first control mode prevails for the periods of time indicated at 18 and 19 in Figure 2a which is a plot of the current through the LED 2 against time.
In the second control mode, the transistor switch 6 is opened when the voltage across the resistor 7 exceeds an input voltage Vpeak fed to a comparator 20. A consequence, the maximum current in each cycle is limited, as indicated at 22 in Figure 2b which is also a plot of LED current against time.
The combination of the first and second control modes is illustrated in
Figure 2c and it this alternating sequence of modes which is imposed on the control circuitry by the mode switch 15. Figure 2c shows two half-rectified waves, corresponding in duration to one cycle of the alternating mains source
1. In this time of one cycle there are four mode changes.
Adjustment of the magnitude of the voltage Vseiect adjusts the threshold voltage at which mode change over takes place so adjustment of the magnitude of Vseiect varies the relative durations of the control modes. Further, adjustment of the voltage Vpw alters the duration of each pulse during the pulse control mode and adjustment of the voltage Vpeak controls the magnitude of the maximum current during the peak current control mode.
It is possible to dispense with the comparator 16 and replace the mode switch 15 with a logic OR.
In a further modification, illustrated in Figure 3, the comparator 20 has a time delay which has the effect of increasing the output current 23, with the result that the power factor is further improved. From reading the present disclosure, other variations and modifications be apparent to persons skilled in the art. Such variations and modifications may involve equivalent and other features which are already known in the art, and which may be used instead of or in addition to features already described herein. Although claims have been formulated in this application to particular combinations of features, it should be understood that the scope of the disclosure of the present invention also includes any novel feature or any novel combination of features disclosed herein either explicitly or implicitly or any generalisation thereof, whether or not it relates to the same invention as presently claimed in any claim and whether or not it mitigates any or all of the same technical problems as does the present invention.
Features which are described in the context of separate embodiments may also be provided in combination in a single embodiment. Conversely, various features which are, for brevity, described in the context of a single embodiment, may also be provided separately or in any suitable subcombination. The applicants hereby give notice that new claims may be formulated to such features and/or combinations of such features during the prosecution of the present application or of any further application derived therefrom.

Claims

1. A switch mode power supply (SMPS) for driving a load, such as an LED (2), from an AC source (1 ), the power supply comprising a rectifying device (3) for delivering an amplitude-varying rectified input voltage from the AC source (1 ), an inductive element (4) for powering the load (2), a switch (6) for repeatedly interrupting the application of the input voltage across the inductive element (4) to create a train of current pulses across the inductive element (4), and a control circuit (12, 13, 14, 15, 16, 17, 20) which controls the switch (6) so that the pulse train is subjected to different control modes during different time intervals of each cycle of the rectified input voltage.
2. An SMPS according to claim 1 , wherein the pulse train is subjected to a pulse width control mode, in which the time duration of each pulse is controlled, during a time interval (18, 19) when the rectified voltage is below a threshold voltage, and wherein the pulse train is subjected to a peak current control mode, in which the magnitude of a current pulse is limited, during a time interval (22) when the rectified voltage is above the threshold voltage.
3. An SMPS according to claim 2, wherein the duration of each pulse is constant during the pulse width control mode (18, 19).
4. An SMPS according to claim 2 or 3, wherein during the peak current control mode (22) a pulse is terminated when the current magnitude reaches a threshold magnitude.
5. An SMPS according to any of claims 2 to 4, wherein the control circuit comprises an oscillator (12) and a bi-stable mode switch (15) which is responsive to the magnitude of the input voltage, the oscillator (12) being arranged to govern the initiation of each pulse and the mode switch (15) being arranged to govern the termination of each pulse.
6. An SMPS according to claim 5, wherein the mode switch (5) is controlled by a comparator (16) responsive to the difference between the magnitude of the input voltage and a reference voltage the magnitude of which is capable of adjustment in order to adjust said threshold voltage so as to vary the relative durations of the control modes.
7. An SMPS according to claim 6, wherein the control circuit additionally comprises two further comparators the outputs of which are fed to the mode switch (15), namely a first further comparator (17) to detect the difference between the magnitude of a high frequency signal produced by the oscillator and a first reference voltage, and a second further comparator (20) to detect the difference between the magnitude of the voltage across a resistor (7) in series with the switch (6) and the inductive element (4) and a second reference voltage, the first comparator (17) being arranged to control the pulse width control mode and the second comparator (20) being arranged to control the peak current control mode.
8. An SMPS according to any of the preceding claims, wherein the inductive element (4) is the primary winding of a transformer (5), the secondary winding (8) of which energises the load (2).
9. An SMPS according to any of the preceding claims, wherein the rectifying device (3) provides half-wave rectification.
PCT/IB2009/052503 2008-06-26 2009-06-11 Switch mode power supplies WO2009156891A1 (en)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
EP08104557.7 2008-06-26
EP08104557 2008-06-26

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Cited By (11)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2012121912A3 (en) * 2011-03-09 2013-04-25 Marvell World Trade Ltd. Two-peak current control for flyback voltage converters
AT13386U1 (en) * 2012-04-13 2013-11-15 Tridonic Gmbh & Co Kg LED converter
WO2013186227A2 (en) * 2012-06-12 2013-12-19 Ikon Semiconductor Limited A constant current switched mode power supply controller
EP2688189A1 (en) * 2012-07-18 2014-01-22 Iwatt, Inc. Hybrid adaptive power factor correction schemes for switching power converters
EP2854485A1 (en) * 2013-08-30 2015-04-01 Helvar Oy Ab PWM dimming
RU2554888C2 (en) * 2013-07-17 2015-06-27 Закрытое акционерное общество "Кантегир" Laser module
US20160020691A1 (en) * 2014-07-15 2016-01-21 Dialog Semiconductor Inc. Hysteretic Power Factor Control Method for Single Stage Power Converters
WO2016209307A1 (en) * 2015-06-26 2016-12-29 Dialog Semiconductor Inc. Flyback pfc converter with adaptive power factor correction
US9681503B2 (en) 2012-04-13 2017-06-13 Tridonic Gmbh & Co Kg Transformer for a lamp, LED converter, and transformer operation method
CN113300587A (en) * 2021-05-18 2021-08-24 西南交通大学 Pulse sequence control method and device for power factor correction converter
AT17617U1 (en) * 2016-12-23 2022-08-15 Tridonic Gmbh & Co Kg Circuit arrangement for operating lamps

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US5134355A (en) * 1990-12-31 1992-07-28 Texas Instruments Incorporated Power factor correction control for switch-mode power converters
WO2006102355A2 (en) * 2005-03-22 2006-09-28 Fairchild Semiconductor Corporation Single-stage digital power converter for driving leds
US20080018261A1 (en) * 2006-05-01 2008-01-24 Kastner Mark A LED power supply with options for dimming

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US4761725A (en) * 1986-08-01 1988-08-02 Unisys Corporation Digitally controlled A.C. to D.C. power conditioner
US5134355A (en) * 1990-12-31 1992-07-28 Texas Instruments Incorporated Power factor correction control for switch-mode power converters
WO2006102355A2 (en) * 2005-03-22 2006-09-28 Fairchild Semiconductor Corporation Single-stage digital power converter for driving leds
US20080018261A1 (en) * 2006-05-01 2008-01-24 Kastner Mark A LED power supply with options for dimming

Cited By (21)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2012121912A3 (en) * 2011-03-09 2013-04-25 Marvell World Trade Ltd. Two-peak current control for flyback voltage converters
AT13386U1 (en) * 2012-04-13 2013-11-15 Tridonic Gmbh & Co Kg LED converter
US9681503B2 (en) 2012-04-13 2017-06-13 Tridonic Gmbh & Co Kg Transformer for a lamp, LED converter, and transformer operation method
WO2013186227A3 (en) * 2012-06-12 2014-03-06 Ikon Semiconductor Limited A constant current switched mode power supply controller
WO2013186227A2 (en) * 2012-06-12 2013-12-19 Ikon Semiconductor Limited A constant current switched mode power supply controller
TWI479786B (en) * 2012-07-18 2015-04-01 Dialog Semiconductor Inc Switching power converter and method of controlling a switching power converter in a controller
EP2688189A1 (en) * 2012-07-18 2014-01-22 Iwatt, Inc. Hybrid adaptive power factor correction schemes for switching power converters
JP2014023428A (en) * 2012-07-18 2014-02-03 Iwatt Inc Hybrid adaptive power factor correction schemes for switching power converters
US8787039B2 (en) * 2012-07-18 2014-07-22 Dialog Semiconductor Inc. Hybrid adaptive power factor correction schemes for switching power converters
US20140022829A1 (en) * 2012-07-18 2014-01-23 Iwatt, Inc. Hybrid Adaptive Power Factor Correction Schemes For Switching Power Converters
CN103580470A (en) * 2012-07-18 2014-02-12 艾沃特有限公司 Hybrid adaptive power factor correction schemes for switching power converters
RU2554888C2 (en) * 2013-07-17 2015-06-27 Закрытое акционерное общество "Кантегир" Laser module
EP2854485A1 (en) * 2013-08-30 2015-04-01 Helvar Oy Ab PWM dimming
US20160020691A1 (en) * 2014-07-15 2016-01-21 Dialog Semiconductor Inc. Hysteretic Power Factor Control Method for Single Stage Power Converters
US9491819B2 (en) * 2014-07-15 2016-11-08 Dialog Semiconductor Inc. Hysteretic power factor control method for single stage power converters
DE112015003287B4 (en) 2014-07-15 2021-08-05 Dialog Semiconductor Inc. Hysteresis power control method for single stage power converters
WO2016209307A1 (en) * 2015-06-26 2016-12-29 Dialog Semiconductor Inc. Flyback pfc converter with adaptive power factor correction
US9584008B2 (en) 2015-06-26 2017-02-28 Dialog Semiconductor Inc. Switching power converter with adaptive power factor correction
AT17617U1 (en) * 2016-12-23 2022-08-15 Tridonic Gmbh & Co Kg Circuit arrangement for operating lamps
CN113300587A (en) * 2021-05-18 2021-08-24 西南交通大学 Pulse sequence control method and device for power factor correction converter
CN113300587B (en) * 2021-05-18 2022-07-15 西南交通大学 Pulse sequence control method and device for power factor correction converter

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